• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
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  • 法律状态
  • 优先权
    • 专利摘要:
    The present invention calculates the Doppler frequency due to fading by counting the number of times the received signal crosses the average received signal level by the level crossing frequency calculator 115, and then receives the received signal obtained from the reference signal correlator 306. The reference signal correlation integration control unit 116 executes control of permission and prohibition in accordance with the Doppler frequency.
    公开号:KR19990036856A
    申请号:KR1019980041658
    申请日:1998-10-02
    公开日:1999-05-25
    发明作者:마사히로 모리야
    申请人:모리시타 요이찌；마츠시타 덴키 산교 가부시키가이샤；
    IPC主号:
    专利说明:

    Receiver
    BACKGROUND OF THE INVENTION 1. Field of the Invention [0001] The present invention relates to a receiving apparatus for saving power. In particular, the present invention relates to a code division multiplex that outputs original transmission information by multiplying transmission information by transmission codes and multiplying the same spreading code by the reception signal. A receiving apparatus using a connection method.
    Code Division Multiple Access (CDMA) is a leading access method in future public land mobile telephone systems, including the US standardized by Qualcomm in the United States as an IS95 for mobile phones. R & D and commercial development are actively being carried out.
    In addition, the CDMA method is a noise-resistant transmission method, and by using a plurality of orthogonal (low correlation) spreading codes, transmission in the same band is possible. It is possible to obtain a double data transfer rate.
    Fig. 1 shows a block diagram of a mobile radio terminal device (hereinafter referred to as a mobile device) using a conventional CDMA system, and will be described. 1 is a schematic configuration example of an IS95 mobile device in a mobile wireless system using a CDMA system.
    The signal (received signal) received at the antenna 301 of the mobile unit is input to the frequency converter 302. The frequency converter 302 mixes the received signal with the frequency (sine wave) output from the frequency synthesizer section 304, thereby converting the frequency from the radio frequency band to the intermediate frequency band. This frequency-converted received signal is output to the orthogonal demodulator 303.
    In addition, a signal transmitted by a base station (not shown) or a signal that is not influenced by fading in a transmission path and has no multipath delay wave is used to convert the reference signal to PNi (t), PNq (t), and amplitude of the reference signal. In order to express Wp (t), the base station carrier frequency ωc, and the information symbol D (t), one channel distinguishing code is used, and it is Wd (t). Can be written as
    The orthogonal demodulator 303 multiplies the received signal by the signals of cos (ωct + φ) and sin (ωct + φ) output from the frequency synthesizer 304, and performs low pass filtering. The I channel baseband signal I (t) and the Q channel baseband signal Q (t) as shown in equations (2) and (3) are generated. Is the phase difference of the carrier frequency of the mobile station with respect to the base station.
    The analog I channel baseband signal I (t) generated by the orthogonal demodulator 303 is converted into a digital signal by the analog / digital (A / D) converter 305a, and the analog Q channel baseband signal Q (t) is converted into a digital signal by the A / D converter 305b, and both digital signals are output to the reference signal correlator 306, the frequency error detector 313, and the reception AGC controller 314.
    The frequency error detection unit 313 detects the phase difference φ between the carrier frequencies of the base station and the mobile station from each of the baseband signals I (t) and Q (t) of the digital and uses a control value to cancel the phase difference φ. The frequency of the unit 304 is adjusted to a predetermined value.
    The receiving AGC (Automatic Gain Control) control unit 314 calculates the received signal level by time-averaging each baseband signal I (t) and Q (t) of the digital, and converts the frequency using a control value which keeps it constant. The reception gain of the unit 302 is controlled. Thereby, even if the input level of the frequency converter 302 changes, the output level becomes constant, and the received signal level is kept constant.
    The reference signal correlator 306 correlates the received signal with the reference signal. Here, correlating means multiplying a transmission signal by a reference signal. The reason for taking the correlation is to remove the reference signal by multiplying the reference signal again because the reference signal is multiplied and transmitted to the transmission data transmitted from the base station.
    In addition, the above-mentioned multiplication is performed by the EXOR circuits (exclusive-OR circuits) 303a and 303b shown in the orthogonal demodulator 303, and the signals of cos (ωct + φ) and sin (ωct + φ). It means to take an exclusive OR of or convert the data " 1 " and " 0 " into " + 1 " and " -1 " This is the same also in the following description.
    Further, by multiplying and correlating the reference signals with each other, the timing of the reference signal included in the received signal can be detected, and by detecting the timing, the mobile unit can synchronize the signal with the base station.
    That is, in the reference signal correlator 306, the received signal is multiplied by the reference signals PNi (t) and PNq (t) generated by the reference signal generator 307, and is represented by the following expression (4). Take
    By this correlation process, a signal (correlation signal) Ipn (t), Qpn (t) indicating a correlation between each digital baseband signal I (t), Q (t) and the reference signals PNi (t), PNq (t) ) Is output to the channel discriminating code correlator 308 and the reference signal correlation integrating unit 311. The correlation signals Ipn (t) and Qpn (t) are represented by the following equations (5) and (6).
    The channel discriminating code correlator 308 multiplies the channel discriminating code Wd (t) generated by the channel discriminating code generator 309 with the correlation signals Ipn (t) and Qpn (t) (in this case, the EXOR circuit By taking an exclusive OR at 308a and 308b, the channel discriminating code Wd (t) is correlated with the received signal, and the correlated signals Iw (t) and Qw (t) are correlated with the code correlation integrating unit ( 310). The correlation signals Iw (t) and Qw (t) are represented by the following equations (7) and (8).
    The code correlation integrating unit 310 for channel discrimination correlates the correlation signals Iw (t) and Qw (t) with one period M of the channel identification code Wd (t) and the reference signal amplitude Wp (t) in the information symbol section. The integral of the section is taken, and the integrated signals I∑w (t) and Q∑w (t) representing this integration result are output to the multiplication value adder 312.
    Here, the reason for taking the integration will be described.
    Since the output after correlation changes at a high rate of n times the information data, it must be lowered at the information data rate, and this is executed by taking the integral. Specifically, for example, the transmission data is set to "1, 0", and the code for distinguishing channels is set to "01010101". Is a signal changing at four times the high speed of the transmission data. In this case, the change of data for each transmission order is as follows.
    Transmission signal 10100101...
    Code for identifying channels 01010101...
    Post-correlation output (correlation signal) 11110000...
    Information data (receive data) 1 0...
    That is, the output after correlation is 11110000... As described above. However, since it changes at four times as fast as the information data, it is necessary to lower it at the information data rate. In this method, for example, there is a method of extracting by 1/4 and a method of taking an average (integral). However, there is a possibility that the reception performance is deteriorated because the extraction may disregard good data. Thus, a method of taking an integration and lowering it at an information data rate is generally used.
    The integrated signals I∑w (t) and Q∑w (t) output from the channel correlation code correlation integrating unit 310 are represented by the following expressions (9) and (10).
    I∑w (t) = MD (T) ⋅ (cosφ-sinφ)
    Q∑w (t) = MD (T) ⋅ (cosφ + sinφ)
    However, T represents symbol time.
    The reference signal correlation integrating unit 311 integrates the correlation signals Ipn (t) and Qpn (t) by M, and multiplies the integral signals I∑pn (t) and Q∑pn (t) representing the result of the integration. Output to section 312. Here, the integration is taken to lower the information rate. This is because the purpose of the data decoding function is to finally restore the information data. Therefore, unless the output signal of the reference signal correlation integrating unit 311 is also made the same as the output signal rate of the code correlation integrating unit 310 for channel discrimination. Because not.
    The integrated signals I∑pn (t) and Q∑pn (t) output from the reference signal correlation integrating unit 311 are represented by the following equations (11) and (12).
    I∑pn (t) = M⋅Wpn (t) ⋅ (cosφ-sinφ)
    Q∑pn (t) = M⋅Wpn (t) ⋅ (cosφ + sinφ)
    Finally, the multiplication value adder 312 takes multiplication value addition of each of the integrated signals I∑w (t), Q∑w (t), I∑pn (t), and Q∑pn (t), Demodulation data (information data) shown in equation (13) is generated.
    Demodulation data = 2M 2 Wpn (t) D (t)
    As described above, in the conventional mobile device, since the reference signal is multiplied and transmitted to the transmission data transmitted from the base station, after multiplying the reference signal again, one information data is integrated for time, and after multiplying the code for distinguishing channels, Integrating the information data time, and taking the sum thereof, removes the code to restore only the information data.
    However, in general, the phase difference φ of the carrier frequency of the base station and the mobile station changes, and the first factor is that the frequency of the frequency synthesizer 304 varies due to temperature change, and the second factor is due to fading. As shown in Fig. 4, it is considered that the power spectrum of the received signal is in the range of the Doppler frequency fD.
    However, the magnification of the power spectrum is 2fD = 2v / λ, which depends on the traveling speed v of the mobile device and the wavelength λ of the transmission wave. As the traveling speed v becomes faster or the wavelength λ becomes shorter (the Doppler frequency fD becomes higher), Grows
    Since the first factor is influenced by temperature, there is little effect on phase change in a short time. However, since the second factor is Doppler frequency fD, a high Doppler frequency fD affects a phase change and a low influence has little effect.
    From this, if the amount of phase change due to the first and second factors is small and the integrated signals I∑pn (t) and Q∑pn (t) output from the reference signal correlation integrating unit 311 hardly change, change them. In other words, when the reference signal correlation integration output hardly changes, the integration process in the reference signal correlation integration unit 311 may not be executed.
    However, in the conventional configuration shown in Fig. 1, even when the reference signal correlation integration output hardly changes, since the reference signal correlation integration process is executed, power consumption increased by that much.
    An object of the present invention is to provide a mobile wireless terminal device using a code division multiple access method that can reduce power consumption.
    According to the present invention, reference signal correlation means for obtaining correlation data by obtaining a correlation between a received signal and a reference signal, reference signal correlation integration means for integrating the correlation data, and counting the number of times the received signal crosses an average received signal level, Level cross-count calculation means for finding the Doppler frequency by fading, and reference signal correlation integration control means for controlling the operation of the reference signal correlation integration means in accordance with the Doppler frequency.
    With this configuration and method, since the reference signal correlation integration control means prohibits the operation of the reference signal correlation integration means depending on the Doppler frequency, the power consumption of the reference signal correlation integration means can be reduced more than if it has always been operating conventionally. Can be.
    It is also an object of the present invention to obtain an internal clock synchronization circuit which can execute synchronization of the internal clock quickly and is realized by a simple circuit configuration.
    1 is a block diagram of a mobile wireless terminal device using a conventional code division multiple access method;
    2 is a block diagram showing the overall configuration of a mobile radio terminal apparatus using the code division multiple access method according to the first embodiment of the present invention;
    3 is a block diagram showing the overall configuration of a mobile radio terminal apparatus using the code division multiple access method according to Embodiment 2 of the present invention;
    4 is a power spectrum distribution diagram by fading;
    Explanation of symbols for the main parts of the drawings
    115: level crossing count calculation unit 116: reference signal correlation integration control unit
    215: frequency magnification measuring unit 301: antenna
    302: frequency converter 303: orthogonal demodulator
    303a, 303b: EXOR circuit 304: Frequency synthesizer section
    305a, 305b: A / D converter 306: reference signal correlator
    307: reference signal generator 308: code correlation unit for distinguishing channels
    308a, 308b: EXOR circuit 309: code generation unit for distinguishing channels
    310: code correlation integrator for distinguishing channels
    311: reference signal correlation integrating unit 312: multiplication value adding unit
    313: frequency error detection unit 314: receiving AGC control unit
    EMBODIMENT OF THE INVENTION Hereinafter, the mobile radio | wireless terminal apparatus using the code division multiple access method which concerns on embodiment of this invention is demonstrated with reference to drawings.
    (Example l)
    2 is a block diagram of a mobile radio terminal apparatus using a code division multiple access method according to Embodiment 1 of the present invention. However, in FIG. 2, the same code | symbol is attached | subjected to the part corresponding to the conventional mobile device in FIG. 1, and the description is simplified.
    The feature of the first embodiment is that, in addition to the conventional configuration, the level crossing frequency calculation section 115 and the reference signal correlation integration control section 116 are provided.
    First, the received signal from the antenna 301 is input to the frequency converter 302. The frequency converter 302 mixes the received signal and the output frequency (sine wave) of the frequency synthesizer 304, converts the frequency from the radio frequency band to the intermediate frequency band, and outputs it to the orthogonal demodulator 303.
    The orthogonal demodulator 303 multiplies the frequency-received received signal by the EXOR circuits 303a and 303b with the signals of cos (ωct + φ) and sin (ωct + φ) output from the frequency synthesizer 304. The low pass filtering process is executed, and the analog I channel baseband signal I (t) and Q channel baseband signal Q (t) thus obtained are output to the A / D converters 305a and 305b.
    The A / D converters 305a and 305b convert analog baseband signals I (t) and Q (t) into digital signals, which are then converted into a reference signal correlator 306, a frequency error detector 313, and a receiver. Output to AGC control unit 314.
    The reference signal correlator 306 correlates the digital baseband signals I (t) and Q (t) with the reference signals PNi (t) and PNq (t) generated by the correlation reference signal generator 307. do. In other words, the reference signals PNi (t) and PNq (t) are correlated with the received signals, and the resultant correlation signals Ipn (t) and Qpn (t) are correlated with the code correlation unit 308 for discriminating the channel and the reference signal. Output to the integrating unit 311.
    The channel discriminating code correlator 308 uses the correlation signals Ipn (t), Qpn (t) and the channel discriminating code Wd (t) generated by the EXOR circuits 308a and 308b. ) By multiplying That is, the correlation between the channel discriminating code Wd (t) and the received signal is taken, and the resultant correlation signals Iw (t) and Qw (t) are output to the channel discriminating code correlation integrating unit 310.
    The code correlation integrating unit 310 for identifying the channel is used to determine the correlation signals Iw (t) and Qw (t) in one information period M of the channel identification code Wd (t) and the amplitude Wp (t) of the reference signal in the information symbol period. Integrates in equal intervals, and outputs the integrated signals I∑w (t) and Q∑w (t) representing this integration result to the multiplication value adder 312.
    Further, the reference signal correlation integrating unit 311 integrates the correlation signals Ipn (t) and Qpn (t) by M, and multiplies the integration signals I∑pn (t) and Q∑pn (t) representing the result of the integration. The value adder 312 outputs the result.
    The multiplication value adder 312 generates demodulation data by taking multiplication value additions of the respective integration signals I∑w (t), Q∑w (t), I∑pn (t), and Q∑pn (t). .
    The frequency error detection unit 313 also detects the phase difference between the carrier frequencies of the base station and the mobile station from each of the baseband signals I (t) and Q (t) of the digital and uses the control value to eliminate the phase difference. The frequency of 304 is adjusted to a predetermined value.
    The reception AGC control unit 314 calculates a reception signal level (average reception signal level) by time-averaging each baseband signal I (t) and Q (t) of the digital, and sets a reception AGC control value for keeping this constant. At the same time as the frequency converter 302, the average received signal level is output to the level crossing frequency calculator 115.
    The level crossing count calculation unit 115 averages the average received signal level for a longer time, and the predetermined number of times that the average received signal level for a short time crosses the average received signal level for a long time in the upward direction (level crossing times) for a predetermined time. Count. By this count, a count value indicating the Doppler frequency is obtained, and output to the reference signal correlation integration control unit 116.
    The reference signal correlation integration control unit 116 controls the processing of the reference signal correlation integration unit 311 based on the count value indicating the Doppler frequency.
    Here, as explained in the conventional example, when the Doppler frequency is low, since the influence of the phase difference of the carrier frequency is hardly influenced, the reference signal correlation integration output hardly changes, and the integration in the reference signal correlation integration unit 311 is performed. It can be seen that the process may not be executed.
    That is, if the count value indicating the Doppler frequency is a value that does not affect the change in the phase difference between the carrier frequency of the base station and the mobile station, the reference signal correlation integration control unit 116 prohibits processing of the reference signal correlation integration unit 311. Take control.
    When the prohibition control is performed, the reference signal correlation integration section 311 outputs the previous reference signal correlation integration values (integral signal) I∑pn (t) and Q∑pn (t) to the multiplication value adder 312. The multiplication value adder 312 generates demodulated data using the value.
    For example, the level crossover frequency calculating section 115 determines that the Doppler frequency is 4 Hz (equivalent to about 5 km / h when the carrier frequency is 900 MHz), and the information symbol rate is 19.2 Kbps. The phase of fluctuates by 0.0013rad.
    This corresponds to a 0.01 dB fluctuation in the phase difference (cosφ-sinφ) included in the integrated signals I∑w (t), Q∑w (t), I∑pn (t), and Q∑pn (t). do. If the reference signal correlation integration control unit 116 suppresses the phase difference (cosφ-sinφ) to 0.5 dB and controls the processing of the reference signal correlation integration unit 311, the reference signal correlation is about 40 symbols at the Doppler frequency of 4 Hz. You only need to permit the integration process once.
    As described above, according to the first embodiment, the level crossing frequency calculation section 115 counts the number of times the average received signal level for a short time intersects the average received signal level for a long time, in other words, the received signal is the average received signal level. The Doppler frequency is calculated by counting the number of times of intersecting , And the reference signal correlation integration control unit 116 executes the control of the processing of the reference signal correlation integration unit 311 based on the Doppler frequency. Power consumption due to unnecessary processing of the unit 311 can be reduced.
    (Example 2)
    3 is a block diagram of a mobile wireless terminal device using a code division multiple access method according to Embodiment 2 of the present invention. 3, the same code | symbol is attached | subjected to the part corresponding to Example 1 in FIG. 2, and the description is abbreviate | omitted. 3, the sign of the signal shown in FIG. 2 is abbreviate | omitted.
    The characteristic of this Embodiment 2 is that the frequency expansion width measuring part 215 is connected between the reference signal correlation integration control part 116 and the frequency error detection part 313 which were demonstrated in Example 1. As shown in FIG.
    The frequency error detection unit 313 detects the phase difference between the carrier frequency of the base station and the mobile station, but the phase difference of the carrier frequency is purely showing the phase difference between the carrier frequency of the base station and the mobile station while the mobile station is stopped. However, it is known that in the state where the mobile unit is moving, it is expanded and distributed by the Doppler frequency under the influence of fading.
    The frequency magnification measurement unit 215 measures the absolute value of the phase difference of the carrier frequency detected by the frequency error detection unit 313 in several steps to obtain an enlargement width of the carrier frequency, and calculates the absolute value of the obtained magnification width of the carrier frequency. It outputs to a reference signal correlation integration control part 116 as a frequency. Moreover, the function of detecting the phase difference of a carrier frequency may be provided in the frequency expansion width measuring part 215.
    Here, the reason why the absolute value of the expansion width of a carrier frequency becomes a Doppler frequency is demonstrated. Doppler frequency is a phenomenon caused by the Doppler effect. As is well known, the Doppler effect is often described by taking sound as an example, and when a stationary person hears this, when the stationary object hears it, it sounds higher than the original sound when the moving object comes closer. When it is far away, it sounds low.
    The high frequency means the deviation in the higher frequency, and the low frequency means the deviation in the lower frequency. The Doppler frequency also generates a frequency deviation with respect to the transmission signal by the frequency calculated from the moving speed / signal wavelength when the mobile is moved. This is because the phenomenon is applied independently to all signals arriving at the mobile station from the base station (signals arriving directly or signals reflected by an object), so that the frequency of the received signal becomes a frequency spectrum extended to the maximum Doppler frequency.
    The reference signal correlation integration control unit 116 performs the control of the processing of the reference signal correlation integration unit 311 in the same manner as described in the first embodiment based on the absolute value indicating the Doppler frequency.
    As described above, according to the second embodiment, the frequency magnification measuring unit 215 obtains the Doppler frequency by measuring the absolute value of the magnification width of the carrier frequency from the phase difference of the carrier frequency detected by the frequency error detection unit 313, and the reference signal correlation integration. Since the control unit 116 executes the control of the processing of the reference signal correlation integrating unit 311 based on the Doppler frequency, power consumption due to unnecessary processing of the reference signal correlation integrating unit 311 can be reduced. have.
    As is apparent from the above description, according to the present invention, since the reference signal correlation integration control means executes the control of the processing of the reference signal correlation integration means in accordance with the Doppler frequency determined by the level crossing frequency calculation means, the reference signal correlation integration means The power consumption can be reduced than when always operating conventionally. Therefore, the power consumption of the mobile radio terminal device can be reduced.
    As mentioned above, although the invention made by this inventor was demonstrated concretely according to the said Example, this invention is not limited to the said Example and can be variously changed in the range which does not deviate from the summary.
    权利要求:
    Claims (10)
    [1" claim-type="Currently amended] Moving speed detecting means for detecting a moving speed of the mobile station apparatus, correlating means for obtaining correlation data by obtaining a correlation between a received signal and a reference signal, an integrator for integrating the correlated data, and operation of the integrating means from the moving speed. And an integration control means for controlling.
    [2" claim-type="Currently amended] The method of claim 1,
    The moving speed detecting means includes calculating means for calculating a Doppler frequency due to fading, and means for detecting the moving speed from the Doppler frequency and the carrier frequency.
    [3" claim-type="Currently amended] The method of claim 2,
    And said calculating means calculates a Doppler frequency due to fading from the number of times a signal value of a received signal crosses an average reception level.
    [4" claim-type="Currently amended] The method of claim 1,
    The moving speed detecting means includes means for calculating an enlargement width of a frequency from a difference between the carrier frequency used by the base station apparatus and the carrier frequency of the mobile station apparatus obtained from the received signal, and the moving speed from the enlargement width of the frequency and the carrier frequency. Receiving means comprising means for detecting.
    [5" claim-type="Currently amended] The method of claim 1,
    The integrating control means stops the operation of the integrating means when the moving speed is lower than a predetermined value.
    [6" claim-type="Currently amended] The method of claim 1,
    And said integrating means holds an output of the integral data obtained immediately before the operation is stopped when the operation is stopped from said integration control means.
    [7" claim-type="Currently amended] A mobile station apparatus for wirelessly communicating a signal spread spectrum spread with a base station apparatus by a spreading code, comprising: the receiving apparatus according to claim 1 for controlling an operation of integrating correlation data between a received signal and a reference signal according to movement speed information; Characterized in that the mobile station apparatus.
    [8" claim-type="Currently amended] A mobile station apparatus for wirelessly communicating a signal spread spectrum by a base station apparatus with a spreading code, comprising: the receiving apparatus according to claim 1 for controlling an operation of integrating correlation data between a received signal and a reference signal according to movement speed information; An information form terminal device.
    [9" claim-type="Currently amended] Calculate the Doppler frequency due to fading from the number of times the received signal crosses the average reception level, measure the moving speed of the mobile station apparatus from the Doppler frequency and the carrier frequency, and correlate the received signal with the reference signal based on the measured moving speed. A receiving method, characterized by controlling the operation of integrating data.
    [10" claim-type="Currently amended] Based on the measured moving speed, the expanded width of the frequency is calculated from the difference between the carrier frequency used by the base station apparatus and the carrier frequency obtained from the received signal, the moving speed of the mobile station apparatus is measured from the expanded frequency and the carrier frequency. And integrating the correlation data of the received signal and the reference signal.
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    同族专利:
    公开号 | 公开日
    EP0913953A2|1999-05-06|
    CA2248516C|2001-09-11|
    CA2248516A1|1999-04-03|
    EP0913953A3|2001-01-31|
    JPH11112470A|1999-04-23|
    JP3391675B2|2003-03-31|
    US6067049A|2000-05-23|
    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    法律状态:
    1997-10-03|Priority to JP97-287942
    1997-10-03|Priority to JP28794297A
    1998-10-02|Application filed by 모리시타 요이찌, 마츠시타 덴키 산교 가부시키가이샤
    1999-05-25|Publication of KR19990036856A
    2001-02-01|Application granted
    2001-02-01|Publication of KR100280027B1
    优先权:
    申请号 | 申请日 | 专利标题
    JP97-287942|1997-10-03|
    JP28794297A|JP3391675B2|1997-10-03|1997-10-03|Mobile radio terminal using code division multiple access system|
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