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    • 专利摘要:
    The invention relates to an antenna (1) comprising a ground plane (11), a metal plate (10) arranged facing said ground plane (11), a feed wire (12) for connecting said plate (10). ) to a generator (16) or a receiver, so that said antenna (1) has a first resonance frequency in plated antenna mode. The antenna (1) further comprises a grounding wire (13) connecting the plate (10) to the ground plane (11), and a capacitive element (15a, 15b, 15c) arranged in series with the wire (13) back to ground between the wire (12) supply and the ground plane (11), so that the antenna (1) further has a second resonance frequency in wire-plate antenna mode.
    公开号:FR3070224A1
    申请号:FR1757731
    申请日:2017-08-18
    公开日:2019-02-22
    发明作者:Cyril Jouanlanne
    申请人:Sigfox SA；
    IPC主号:
    专利说明:

    TECHNICAL AREA
    The present invention belongs to the field of antennas. An antenna is a device used to radiate (emitter) or pick up (receiver) electromagnetic waves. In particular, the invention relates to an antenna whose structure makes it possible to radiate or receive radio waves at two distinct working frequencies according to two different radiation modes and with particularly advantageous performance.
    STATE OF THE ART
    In the field of compact antennas used for telecommunications, the antennas known to those skilled in the art are already known by the name of "plated antenna". These antennas are also known under the name of "printed antenna", or under the anglicism "patch antenna".
    Such an antenna consists of a radiating element corresponding to a metal plate of any shape (rectangular, circular, or other more elaborate shapes) generally deposited on the surface of a dielectric substrate which has on the other face a conducting plane, or plane massive. The dielectric substrate, which essentially acts as a mechanical support for the radiating element, can be replaced by a honeycomb structure whose behavior is similar to that of air, or even be eliminated if the mechanical maintenance of the radiating element can be provided by other means. The antenna is generally supplied via a supply wire consisting of a coaxial probe which crosses the ground plane and the substrate and is connected to the radiating element, that is to say ie to the plate.
    However, a plated antenna has the disadvantage of having relatively large dimensions, of the order of half the wavelength of the desired working frequency. Indeed, we can consider as a first approximation that a plated antenna with a rectangular plate behaves like a cavity whose various discrete resonance frequencies correspond to known modes depending on the dimensions of the plate. In particular, for a so-called "fundamental" mode, the antenna resonates at a frequency of which half the wavelength corresponds to the length of the cavity. Thus, the lower the desired working frequencies, the larger the dimensions of the radiating element so that at least one of the resonant frequencies of the cavity coincides with the working frequency.
    To overcome this problem and reduce the size of the antennas, there are also known antennas known to the skilled person under the name of "wire-plate antenna". Compared to a plated antenna, a wire antenna has at least one additional conductive wire connecting the plate to the ground plane. It is a return wire to the active mass and radiating at the working frequency considered.
    Such a wire-plate antenna is the seat of two resonance phenomena, one relating to a series type resonance employing all the elements constituting the structure of the antenna, and the other relating to a resonance of parallel type using the only elements due to the ground wire and to the capacitor formed by the plate (also sometimes called “capacitive roof”) and the ground plane. This is why we sometimes speak of "double resonance" for wire-plate type antennas. The so-called parallel resonance caused by the return wire to ground of a wire-plate antenna takes place at a frequency lower than that of the fundamental resonance frequency of the cavity type of a plated antenna. Thus, for given plate dimensions, a wire-plate antenna has a lower working frequency than a plated antenna.
    It should be noted that the operation of a wire-plate antenna is very different from the operation of a plated antenna. Indeed, the resonance of which one speaks for a plated antenna is of electromagnetic type: resonance of a cavity formed by the ground plane, the plate and the four imaginary "magnetic walls" connecting the four edges of the plate to the plane of mass. As for the resonance of a wire-plate antenna, it is of the electrical type: the resonant elements are localized, comparable to electrical components.
    However, it is sometimes desirable to have an antenna which is capable of operating at several distinct working frequencies, and with different radiation modes, in order to respond to different functions. These separate working frequencies can for example belong to discontinuous frequency bands sometimes distant by several hundred megahertz from each other.
    For this purpose, it is known to combine several antennas on a single structure. For example, it is known to superimpose several wire-plate type antennas, or else to superpose a plated type antenna and a wire-plate type antenna, in order to obtain an antenna behavior which would be equivalent to that of several separate antennas. However, these solutions have several drawbacks, notably a space requirement of the antenna, a mechanical complexity which increases its manufacturing cost, as well as difficulties in adapting the antenna to the different working frequencies, which results in degraded performance of the antenna. .
    STATEMENT OF THE INVENTION
    The object of the present invention is to remedy all or part of the drawbacks of the prior art, in particular those set out above.
    To this end, and according to a first aspect, the present invention relates to an antenna comprising a ground plane, a metal plate arranged opposite said ground plane, a supply wire making it possible to connect said plate to a generator or a receiver, a ground return wire connecting the plate to the ground plane, as well as a capacitive element arranged in series with the ground return wire between the supply wire and the ground plane.
    With such arrangements, the antenna not only has a resonance in plated antenna mode (that is to say an electromagnetic type cavity resonance) at a first working frequency, but also a resonance in wire-plate antenna mode (i.e. an electrical type resonance) at a second working frequency lower than the first working frequency. Each of these two resonances corresponds to a particular radiation mode. The capacitive element makes it possible in particular to optimize the radiation power of the antenna as well as its adaptation in impedance to the two working frequencies considered.
    In particular embodiments, the invention may also include one or more of the following characteristics, taken in isolation or in any technically possible combination.
    In particular embodiments, the antenna plate is a rectangular plate, two opposite angles of the same diagonal are truncated so that the antenna has a circular polarization at the first working frequency.
    In particular embodiments, the capacitive element is a discrete electronic component.
    In particular embodiments, the capacitive component is of controllable capacitive value.
    In particular embodiments, the capacitive element comprises two electrodes, one of which is formed by a metal plate located at one end of the ground return wire and arranged opposite the antenna plate or the ground plane. .
    In particular embodiments, the metal plate of the capacitive element is located at the end of the earth return wire on the side of the antenna plate, so that the other electrode is formed by the plate of the antenna.
    In particular embodiments, a slot is made in the antenna plate, so that said slot completely surrounds the connection point between the ground wire and the plate, and the capacitive element comprises two electrodes one electrode of which is formed by a portion of the antenna plate which is outside a periphery formed by the slot, and the other electrode of which is formed by another portion of the antenna plate which is inside said periphery formed by the slot.
    In particular embodiments, at least one of the grounding and feeding wires is a metal strip cut from the antenna plate.
    In particular embodiments, the distance between the supply wire and the ground return wire is greater than one tenth of the wavelength of the second working frequency.
    According to a second aspect, the invention relates to a transmission device comprising an antenna according to any one of the preceding embodiments and a generator connected to the supply wire, adapted to form an electrical signal at the first working frequency and / or at the second working frequency.
    According to a third aspect, the invention relates to a reception device comprising an antenna according to any one of the preceding embodiments and a receiver connected to the supply wire, adapted to receive an electrical signal at the first working frequency and / or at the second frequency of work.
    According to a fourth aspect, the invention relates to a transceiver device comprising an antenna according to any one of the preceding embodiments, configured to receive a signal at the first working frequency comprising geolocation information transmitted by a satellite communication system and for transmitting to a terrestrial wireless communication system a signal at the second working frequency comprising the geographical position of said device.
    PRESENTATION OF THE FIGURES
    The invention will be better understood on reading the following description, given by way of nonlimiting example, and made with reference to FIGS. 1 to 15 which represent:
    - Figure 1: a schematic representation, according to a perspective view, of a first embodiment of an antenna according to the invention,
    - Figure 2: a schematic representation, in a sectional view in a vertical plane, of the first embodiment of the antenna,
    - Figure 3: a schematic representation of the shape of the plate for the first embodiment of the antenna,
    - Figure 4: a schematic representation of a variant of the first embodiment of the antenna,
    - Figure 5: a schematic representation of the plate for a variant of the first embodiment of the antenna,
    - Figure 6: a diagram representing the reflection coefficient at the input of the antenna for the first embodiment,
    - Figure 7: a radiation diagram according to a vertical section plane for the first embodiment of the antenna and for a first working frequency,
    - Figure 8: a radiation diagram according to a vertical section plane for the first embodiment of the antenna and for a second working frequency,
    - Figure 9: a diagram representing the reflection coefficient at the input of the antenna for different values of a capacitive element,
    - Figure 10: a schematic representation, in a sectional view in a vertical plane, of a second embodiment of the antenna,
    - Figure 11: a diagram representing the reflection coefficient at the input of the antenna for the second embodiment,
    - Figure 12: a radiation diagram according to a vertical section plane for the second embodiment of the antenna and for a first working frequency,
    - Figure 13: a radiation diagram according to a vertical section plane for the second embodiment of the antenna and for a second working frequency,
    - Figure 14: a schematic representation of the antenna plate for a third embodiment,
    - Figure 15: a diagram representing the reflection coefficient at the input of the antenna for the third embodiment,
    In these figures, identical references from one figure to another denote identical or analogous elements. For the sake of clarity, the elements shown are not to scale, unless otherwise stated.
    DETAILED DESCRIPTION OF EMBODIMENTS
    As indicated above, the present invention relates to an antenna 1 whose structure makes it possible to radiate or receive electromagnetic waves at two distinct working frequencies according to two different radiation modes and with particularly advantageous performance.
    In the following description, we place ourselves by way of example and in no way limitative, in the case where such an antenna 1 is integrated in a connected object intended to be placed for example on the roof of a motor vehicle and configured to receive a signal from a satellite geolocation system (also known in English by the acronym GNSS for Global Navigation Satellite System), such as for example the GPS system (Global Positioning System), in order to determine its geographical position, and to transmit it, possibly accompanied by other information, to another wireless communication system such as, for example, an access network of the “Internet of Things” type, or loT (English acronym for “Internet Of Things”).
    To receive a signal from a geolocation system by satellite, the antenna 1 must preferably have a high gain in a vertical direction 18 and upwards relative to the roof of the vehicle at the working frequency of said geolocation system. If we consider for example the GPS system, the working frequency, that is to say the frequency of the radio signals emitted by the GPS satellites, is approximately 1575 MHz. Also, the polarization used by the GPS system, that is to say the polarization of the electric field of the wave emitted by an antenna of a GPS satellite, is a right circular polarization, called RHCP (acronym for Right Hand) Circular Polarization).
    To transmit information to a loT type wireless communication system, it is on the other hand advantageous for the antenna 1 to present, at the working frequency of said communication system, an omnidirectional gain which is maximum in a substantially parallel horizontal plane. on the roof of the vehicle. Indeed, the base stations of an access network of such a wireless communication system are generally located on the sides relative to the vehicle, and not vertically. In the following description, we place ourselves by way of example and without limitation in the case of an ultra narrow band wireless communication system. By “ultra narrow band” (“Ultra Narrow Band” or UNB in Anglo-Saxon literature) is meant that the instantaneous frequency spectrum of the radio signals emitted is of frequency width less than two kilohertz, or even less than one kilohertz. Such UNB wireless communication systems are particularly suitable for applications of the loT type. They can for example use the ISM frequency band (acronym of "Industrial, Scientific and Medical") located around 868 MHz in Europe, or the ISM frequency band located around 915 MHz in the United States. A rectilinear polarization is generally used in such systems.
    Thus, for the remainder of the description, we place ourselves in the case where the antenna 1 according to the invention operates at two distinct working frequencies: a first working frequency close to 1575 MHz corresponding to the frequency of the GPS system, and a second working frequency located in an ISM band supported by the loT type wireless communication network considered, for example the 868 MHz band or the 915 MHz band.
    FIG. 1 schematically represents, in a perspective view, a first embodiment of such an antenna. In the example illustrated in FIG. 1, the antenna 1 comprises a first radiating element in the form of a metal plate 10 of square shape. According to other examples, the plate 10 could be rectangular, hexagonal, circular, or of any other shape.
    The plate 10 is arranged opposite a ground plane 11. In the following description, it is considered, without limitation, that the plate 10 is planar. However, according to other examples, nothing excludes having a non-planar plate 10. In addition, it is considered that the plate 10 is arranged horizontally and in a manner substantially parallel with respect to the ground plane 11. According to other alternative examples, the plate 10 may be slightly inclined relative to the ground plane 11. The distance separating the plate 10 of the ground plane 11 is much smaller than the dimensions of the plate 10 and the wavelengths of the working frequencies of the antenna. For example, this distance is at least less than a tenth of the wavelength of the first working frequency. The two metal surfaces corresponding to the plate 10 and to the ground plane 11 can for example be arranged on either side of a dielectric substrate 14 which then plays the role of mechanical support. In other examples, the dielectric substrate 14 can be replaced by a honeycomb structure whose behavior is close to that of air, or it can be eliminated if the mechanical maintenance of the plate 10 relative to the ground plane 11 is provided by other means. The dimensions of the ground plane 11 are generally greater than those of the plate 10. In the example considered where the antenna is integrated in a connected object intended to be placed on the roof of a motor vehicle, the metal roof of the vehicle can also play the role of a ground plane whose dimensions are very large compared to the dimensions of the plate 10. The importance of the dimensions of the plate 10 and the ground plane 11 will be discussed later in the description.
    The plate 10 and the ground plane 11 are connected by means of a supply wire 12. The supply wire 12 can for example be, in a conventional manner, a coaxial probe which crosses the ground plane 11 and the dielectric substrate 14 and is connected to the plate 10.
    In addition, the antenna 1 comprises a wire 13 returning to ground which connects the plate 10 to the ground plane 11. As will be detailed later, this wire 13 returning to ground plays the role of a second radiating element at the second working frequency. Preferably, the power supply wire 12 and / or the ground return wire 13 are arranged substantially perpendicular to the ground plane. In the case where the feed wire 12 and the return wire 13 are both perpendicular to the ground plane 11 and to the plate 10, then they are further arranged substantially parallel between said ground plane 11 and said plate 10.
    More generally, the term "wire" means a conductor of any cross section, not necessarily circular. In particular, the feed wire 12 and / or the return wire 13 could be a metallic strip.
    In transmission, the antenna 1 converts an electric voltage or current existing in the supply wire 12 into an electromagnetic field. This electrical supply is for example provided by a generator 16 of voltage or current.
    Conversely, on reception, an electromagnetic field received by the antenna 1 is converted into an electrical signal which can then be amplified.
    In general, a passive antenna can be modeled by a component having a certain impedance seen at the input of the antenna. It is a complex impedance, the real part of which corresponds to the "active" part of the antenna, that is to say a dissipation of energy by ohmic losses and electromagnetic radiation, and whose imaginary part corresponds to the “reactive” part of the antenna, that is to say storage in the form of electrical energy (capacitive behavior) and magnetic energy (inductive behavior). If at a particular frequency, called resonant frequency, the inductance and the capacity of the antenna are such that their effects cancel each other out, then the antenna is equivalent to a pure resistance, and if the ohmic losses are negligible the power supplied to the antenna is almost entirely radiated. Such behavior is observed if the imaginary part of the antenna is zero.
    On the other hand, to ensure maximum power transfer between a power source and an antenna, it is necessary to ensure an impedance matching. The adaptation makes it possible to cancel the reflection coefficient, conventionally denoted Su, at the input of the antenna. The reflection coefficient is the ratio between the reflected wave at the input of the antenna and the incident wave. If the adaptation is not ensured, part of the power is returned to the source. In practice, to ensure good impedance matching, the antenna must have an impedance equal to that of the transmission line, generally 50 ohms.
    In other words, to obtain an optimal behavior of the antenna 1 in terms of radiation, it is necessary to make it behave, for the generator which supplies it and at a predetermined resonant frequency, like a load of which the part real value is close to a determined value, most often 50 ohms, and the imaginary part of which is zero or almost zero. To this end, it is common to insert between the generator 16 and the antenna 1 an electronic circuit for transforming impedance, called “matching circuit” 17, which modifies the input impedance of the antenna 1 view from the source and ensures impedance matching. Such an adaptation circuit 17 can for example include passive elements such as filters based on inductances and capacitors or transmission lines.
    The plate 10 and the ground plane 11 can be likened to a resonant cavity which can be considered, at low frequency, as a capacitance which stores charges and in which a uniform electric field is created between the ground plane 11 and the plate 10. As long as the distance between the ground plane 11 and the plate 10 is small compared to the wavelength of the frequencies considered, the electric field is oriented along an axis perpendicular to the horizontal plane containing the ground plane 11. At high frequency , the distribution of the charges on the plate 10 is no longer uniform, and this is also the case for the distribution of the current and that of the electric field. A magnetic field also appears. It is then known that for particular frequencies, called cavity resonance frequencies, linked to the dimensions of the cavity (that is to say linked to the dimensions of the plate 10), the distribution of the electric field is such that the radiation of the antenna is optimized. Such frequencies F mn are defined according to the expression below by couples (m, n) where m and n are integers greater than or equal to 0, at least one of m or n being non-zero, which represent cavity modes:
    expression in which:
    - c is the speed of light in a vacuum e r is the relative permittivity for the dielectric substrate 14
    - L is the length of the plate 10
    - / is the width of the plate 10
    It then becomes clear that if we consider that the relative permittivity is close to 1 (for example in the case where the dielectric substrate 14 is replaced by ambient air), for a mode, called fundamental cavity resonance mode, for which m is 1 and n is 0, the resonant frequency is such that half of its wavelength corresponds to the length L of the plate. It should be noted that for the example considered described with reference to FIG. 1, the length L and the width / are both equal to the length of one side of the plate 10 which is square in shape.
    Thus, radiation with an electromagnetic type cavity resonance can for example be obtained for a first working frequency of 1575 MHz by using a length of one side of the plate 10 close to 9 cm, that is to say approximately half the length. wave corresponding to this frequency. Other parameters such as for example the distance separating the plate 10 from the ground plane 11 or the value of the permittivity of the dielectric substrate 14 can however influence the length of the plate 10 for which a cavity resonance is obtained. In the example considered for the first embodiment, the plate 10 is a 8.5 cm side square. At the first working frequency of 1575 MHz, the antenna 1 then has a behavior close to that of a plated antenna. The impedance adaptation of such an antenna is generally obtained when the feed wire 12 is positioned at one side of the plate 10 rather than towards its central area.
    On the other hand, the plate 10 and the wire 13 returning to ground can play the role of two elements having a radiating behavior of the electrical type. The antenna 1 then has a behavior close to that of a wire-plate antenna. The antenna 1 can in particular be the seat of a parallel type resonance implementing the wire 13 returning to ground and the capacitor formed by the plate 10 and the ground plane 11. This so-called parallel resonance caused by the wire 13 of return to ground takes place at a frequency lower than that of the fundamental resonance frequency of cavity type mentioned above.
    If the shape of the plate 10 is not decisive for this electrical type radiation, the value of its surface has an impact on the working frequency. In particular, the smaller the surface of the plate 10, the higher the wire-plate type resonance frequency. For a square plate 10, the wire-plate type resonant frequency is generally such that a quarter of its wavelength is close to the length of one side of the plate 10, but again other parameters of the structure of antenna 1 can influence the resonant frequency. In the example considered for the first embodiment, radiation of the electrical type is obtained for a second working frequency of 868 MHz.
    It should be noted that it would be possible to obtain a second higher working frequency by reducing the surface of the plate 10, for example by using a rectangular plate of length L fixed relative to the wavelength of the first working frequency, and advantageously choosing the width / of the plate to obtain the desired second working frequency.
    It should be noted that the two operating modes of the antenna 1 described above are fundamentally different. Indeed, it is a question on the one hand, at a frequency of 1575 MHz, of an electromagnetic type resonance (resonance in plated antenna mode) corresponding to the resonance of a cavity formed by the ground plane 11, the plate 10 and the four imaginary “magnetic walls” connecting the four edges of the plate 10 to the ground plane 11, and on the other hand, at a frequency of 868 MHz, an electrical type resonance (resonance in wire antenna mode -plate), that is to say a resonance for which the resonant elements are localized, comparable to electrical components (in particular, the assembly formed by the ground plane 11 and the plate 10 is comparable to a capacity while the wire 13 of return to ground has an inductance). In the production of such an antenna 1, a great difficulty lies in the possibility of adapting the antenna 1 in impedance for the two operating modes corresponding to two different radiation modes.
    Many parameters influence the impedance matching of antenna 1, such as the position of the feed wire 12, that of the return wire 13, the distance separating the feed wire 12 from the wire 13 back to ground, their diameter, etc. It is therefore possible to play on these different parameters to obtain the best possible impedance matching.
    It is also possible to play on the adaptation circuit 17 to improve this impedance adaptation. However, the performance of an antenna is generally better if it is adapted in impedance by its own structure rather than by an adaptation circuit inserted between the generator and the antenna 1.
    It is generally pointless to be able to adapt the antenna 1 described above in impedance for the two working frequencies considered by using only the above-mentioned parameters and / or by placing an adaptation circuit 17 between the antenna 1 and the generator 16, while maintaining reasonable performance of the antenna. This is why an additional capacitive element 15a is placed in series with the wire 13 returning to ground between the supply wire and the ground plane 11. As explained previously, it is a question of ensuring that the antenna 1 behaves, for the generator 16 which supplies it and at a predetermined resonant frequency, like a load whose real part is close to a determined value, usually 50 ohms, and whose imaginary part is zero or almost zero. The capacitive element 15a has an impedance which depends on its capacitive value and the frequency used. It thus modifies the impedance of the antenna 1 and can make it possible to obtain an adaptation in impedance to the two working frequencies considered. It can in particular compensate for the inductance represented by the wire 13 returning to ground.
    It should also be noted that in order to obtain an electrical type resonance at the second working frequency, it is important that an inductive coupling exists between the supply wire 12 and the return wire 13. These two wires must therefore be close enough to each other. However, it turns out that the impedance matching of the antenna 1 to the first working frequency is better if the supply wire 12 is positioned at one side of the plate 10 while the return wire 13 to ground should rather be positioned towards the central area of the plate 10. Indeed, as will be detailed later with reference to Figure 8, it is important that the return wire to ground is positioned towards the middle of the plate 10 to optimize the monopolar type radiation with a rectilinear polarization at the second working frequency. In addition, to obtain a cavity-type resonance at the first working frequency, it is important that the electric current flowing through the wire 13 returning to ground at this frequency is as low as possible. This can be favored by positioning the wire 13 returning to ground at a point corresponding to an electric field node at the first working frequency, that is to say at a point where the electric field is particularly weak, or even almost zero, at the first working frequency. This is particularly the case in the middle of plate 10.
    This relatively large distance between the feed wire 12 and the ground return wire 13 is one of the elements which distinguishes the antenna 1 according to the invention from conventional wire-plate antennas for which this distance must generally be less than a tenth of the wavelength of the working frequency considered, which is not the case for the antenna 1 according to the invention.
    Figure 2 shows schematically in a sectional view in a vertical plane the first embodiment of the antenna 1 described above with reference to Figure 1. This sectional view allows in particular to see that the wire 12 supply crosses the ground plane 11 to be connected to a generator 16 or else to a receiver. It should be noted that the supply wire 12 must in this case be isolated from the ground plane 11 where it crosses it.
    The capacitive element 15a used in this first embodiment is a discrete electronic component, for example a capacitor, connected on one side to the ground plane 11 and on the other side to the wire 13 returning to ground.
    FIG. 2 also makes it possible to clarify what is meant by the vertical direction 18. This is the upward direction perpendicular to the plane containing the ground plane 11 which is considered horizontal. We can then define an angle Θ formed between this vertical direction 18 and another direction. This angle will be of particular interest in defining the radiation of the antenna 1 in the different directions of space.
    FIG. 3 is a schematic representation of the shape of the plate 10 for a particular embodiment of the antenna 1. As indicated previously, the polarization of the electric field of the wave emitted by an antenna of a GPS satellite is a right circular polarization (RHCP). To obtain such a polarization for the electromagnetic wave radiated by the antenna 1 at the first working frequency, two opposite angles on the same diagonal of the plate 10 are truncated. In the example considered for the first embodiment, the part truncated at each of said angles is an isosceles right triangle whose hypotenuse is 25 mm long.
    However, it should be noted that there are other means of obtaining circular polarization, such as by exciting the antenna 1 with two sources 90 ° out of phase.
    Figure 4 is a schematic representation of a variant of the first embodiment described with reference to Figures 1 to 3 for which the wire 13 returning to ground crosses the ground plane 11. In this case, the wire 13 returned to ground must be isolated from ground plane 11 where it crosses it. The capacitive component 15a is then connected on one side to ground and on the other side to the end of the ground return wire 13 which has passed through the ground plane 11. Advantageously, the ground return wire 13 ground and / or the feed wire 12 can then serve as a mechanical support for the plate 10 relative to the ground plane 11.
    The main characteristics of the first embodiment of the antenna 1 described above with reference to Figures 1 to 4 are given below by way of non-limiting example. Plate 10 is a square 8.5 cm side. The distance separating the ground plane 11 from the plate 10 is 10 mm. The dimensions of the ground plane 11 are not decisive, but in the example considered they are of the order of three to four times those of the plate 10. The feed wire 12 has a diameter of 1 mm and it is positioned at the middle of one of the sides of the plate 10, at a distance equal to 10 mm from said side. The return wire 13 has a diameter of 4 mm and is positioned in the center of the plate 10. The distance separating the supply wire 12 from the return wire 13 is therefore approximately 32.5 mm. The value of the capacitive component 15a is 21.3 pF. The matching circuit 17 is a conventional series / parallel circuit (so-called "L" circuit) involving an inductance of 12.6 nH and a capacitor of 2 pF.
    FIG. 5 is a schematic perspective representation of the plate 10 of the antenna 1 for a variant of the embodiment described with reference to FIG. 4. In this variant, the supply wire 12 and the return wire 13 the mass are two metal ribbons cut from the plate 10 and folded perpendicular to the plate. The dimensions of the slots corresponding to the recesses due to the cuts in the plate 10 are sufficiently small (for example about 3 mm wide) to have no effect on the performance of the antenna. A particularly interesting aspect of this variant is to simplify the manufacture of the antenna since it is then no longer necessary to connect wires to the plate 10. The metal ribbons in fact play the role of the supply wire 12 and the wire 13 returning to ground and they are integral with the plate 10. The metal ribbons, since they are rigid by nature, can also play the role of mechanical support for the plate 10 relative to the ground plane 11.
    FIG. 6 is a diagram which represents the reflection coefficient at the input of antenna 1 for the first embodiment described above with reference to FIGS. 1 to 4. In general, the reflection coefficient, conventionally noted Su and expressed in dB, is the ratio between the reflected wave at the input of an antenna and the incident wave. It depends on the input impedance of the antenna and the impedance of the transmission line that connects the generator to the antenna.
    The curve 20 represents the evolution of the reflection coefficient Su of the first embodiment of the antenna 1 as a function of the frequency. A resonant frequency corresponding to the first working frequency of 1575 MHz is indicated by the triangular marker No. 3. Another resonant frequency corresponding to the second working frequency of 868 MHz is indicated by the triangular marker No. 2. Each resonant frequency corresponds to a minimum of the reflection coefficient Su. It takes a value close to -13 dB for the resonance at 1575 MHz, and a value close to -16 dB for the resonance at 868 MHz. A minimum value of the reflection coefficient generally corresponds to a frequency for which the antenna is adapted in impedance. A typical criterion is to have for example a reflection coefficient of less than -10dB on the pass band of the antenna, that is to say on the frequency band for which the transfer of energy from the power supply to the antenna (or from the antenna to the receiver) is maximum The curve 20 therefore makes it possible to confirm that with the characteristics previously listed for the first embodiment described with reference to FIGS. 1 to 4, the antenna 1 is suitable impedance at the two working frequencies considered.
    FIG. 7 represents a radiation diagram according to a vertical section plane for the first embodiment of the antenna 1 for the first working frequency of 1575 MHz. It represents the variations of the power radiated by the antenna 1 in different directions of space. It indicates in particular the directions of space in which the radiated power is maximum.
    Curve 22a corresponds to radiation according to right circular polarization (RHCP). It has a single lobe, the main direction of which is oriented vertically 18 (Θ = 0 °) upwards. It is in this direction that the energy emitted or received by the antenna is maximum. The maximum gain is approximately 10 dBi, and a 3 dB opening angle of approximately 60 ° is observed.
    Curve 22b corresponds to radiation according to the left circular polarization (LHCP). It has a lobe in the vertical direction 18 upwards and another lobe in a direction at 60 ° from the vertical 18 (Θ = 60 °). For these two directions, the maximum gain is only about -10 dBi. Thus, there is about 20 dB of gain difference between the RHCP polarization and the LHCP polarization in the vertical direction 18 upwards. These values make it possible to obtain a good discrimination of the two types of circular polarizations in this direction. The antenna 1 is thus particularly efficient in RHCP polarization at the first working frequency of 1575 MHz in this vertical direction 18 and upwards. It is therefore quite suitable for receiving signals from satellites of the GPS system.
    FIG. 8 represents a radiation diagram according to a vertical section plane for the first embodiment of the antenna 1 for the second working frequency of 868 MHz.
    The curve 21 corresponds in particular to the radiation of the antenna 1 at this frequency according to a rectilinear polarization along the vertical 18. It is significant of an omnidirectional radiation of the monopolar type (that is to say corresponding to the radiation of a monopoly). One can in particular observe a lobe with symmetry of revolution. The radiation is maximum horizontally, that is to say parallel to the ground plane (Θ = 90 °), and it is zero vertically, that is to say perpendicular to the latter (Θ = 0 °). The antenna has a gain of approximately 5 dBi in the horizontal directions (Θ = 90 °). There is a loss of more than 3 dB of gain with respect to the maximum gain for angles Θ with respect to the vertical 18 less than or equal to about 40 °. The position of the wire 13 returning to ground in the middle of the plate 10 advantageously makes it possible to favor this omnidirectional radiation of the monopolar type with a rectilinear polarization inscribed in a plane containing the wire 13 returning to ground (the electric field of the electromagnetic wave radiated or received by the antenna keeps a fixed direction along the axis of the wire 13 returning to ground, that is to say along the vertical 18). The antenna 1 is thus particularly efficient in rectilinear polarization at the second working frequency of 868 MHz in mainly horizontal directions. It is therefore entirely suitable for transmitting signals to an loT type access network operating around this frequency.
    It should be noted that the radiation diagrams in FIGS. 7 and 8 show radiation only in the space above the ground plane 11 of the antenna 1 (-90 ° <Θ <90 °). This is because the dimensions of the ground plane 11 are large enough relative to the dimensions of the plate 10 so that it reflects the waves emitted by the antenna upwards. For example, the dimensions of the ground plane 11 are at least ten times greater than those of the plate 10, this is particularly the case when the roof of the motor vehicle acts as a ground plane.
    FIG. 9 represents the reflection coefficient Su at the input of the antenna 1 for different values of the capacitive component 15a.
    Curve 23 represents the reflection coefficient Su for a first capacitance value of 21.3 pF for which an electrical type resonance is obtained for a second working frequency close to 868 MHz (which belongs for example to an ISM frequency band in Europe for the loT network considered). The triangular marker No. 4 indicates a minimum value of Su less than -16 dB for this frequency.
    Curve 24 represents the reflection coefficient Su for a second capacitance value of 17 pF for which an electrical type resonance is obtained for a second working frequency close to 893 MHz (which belongs for example to an ISM frequency band in the States United for the loT network considered). The triangular marker No. 3 indicates a minimum value of Su of the order of -15 dB for this frequency.
    Curve 25 represents the reflection coefficient Su for a third capacitance value of 13.8 pF for which an electrical type resonance is obtained for a second working frequency close to 923 MHz (which belongs for example to an ISM frequency band in Australia or in Japan for the loT network considered). The triangular marker n ° 1 indicates a minimum value of Su of the order of -14 dB for this frequency.
    For these three values of the capacitive component 15a, a fundamental resonance frequency of cavity type is always obtained for the first working frequency of 1575 MHz. The triangular marker No. 2 indicates a minimum value of Su of the order of -14 dB for this frequency.
    Experience shows that it is possible, for example, to vary the value of the capacitance of the capacitive component 15a from 10 pF to 50 pF to obtain an electrical type resonance for a second working frequency varying between 800 MHz and 1 GHz. The higher the value of the capacitance, the lower the value of the second working frequency for which an electrical type resonance is obtained. For this range of values of the capacitance of the capacitive component 15a between 10 pF and 50 pF, the operation of the antenna 1 at the first working frequency is not impacted. For values of the capacitance of the capacitive component 15a of less than 10 pF or greater than 50 pF, it no longer seems possible to adapt the antenna 1 for the two desired radiation modes.
    Thus, it is very easy to adapt the manufacture of an antenna 1 according to the geographical area in which it is intended to operate. It suffices to change the capacitive value of the capacitive component 15a to obtain a value of the second working frequency corresponding to the operating frequency of the loT type access network for the geographic area considered. It is also possible to use a capacitive component 15a whose capacitive value is controllable, for example a variable capacitor, a varicap diode (from the English “variable capacitor”, a DTC component (acronym for “Digitally Tunable Capacitor”) , or else a switch to different capacities, so that a single antenna 1 can operate in different geographic areas where different working frequencies of the loT type access network are used.
    FIG. 10 is a schematic representation, according to a sectional view in a vertical plane, of a second embodiment of the antenna 1.
    In this second particular embodiment, the capacitive element 15b comprises two electrodes, one of which is a metal plate 19 placed opposite the plate 10 which corresponds to the other electrode. The capacitive element 15b is therefore once again placed in series with the wire 13 returning to ground between the supply wire 12 and the ground plane 11. In the example illustrated in FIG. 10 for this second embodiment , the plate 19 is placed at the end of the return wire 13 which is on the side of the plate 10, but nothing would, according to another example, place it at the other end of the wire 13 back to ground which is on the side of the ground plane 11 (in this case, it is the ground plane 11, and not the plate 10, which corresponds to the other electrode of the capacitive element 15b).
    In this second embodiment, it is possible for example to use a printed circuit 31 (PCB in English for “Printed Circuit Board”), one face of which is entirely metallized to make the plate 10, and of which only a small area of 1 the other face is metallized to make the lower plate 19 of the capacitive element 15b. This allows in particular to facilitate the manufacture of the antenna 1 because the wire 13 returning to ground can then play the role of mechanical support for the printed circuit 31 which comprises both the plate 10 and the capacitive element 15b. In the example considered for this second embodiment, the plate 19 is a disc with a diameter of 10 mm and the distance between the plate 19 and the plate 10 is 0.1 mm.
    Furthermore, in this second embodiment, the impedance matching of the antenna 1 is carried out only by playing on the different parameters of the structure of said antenna. The adaptation circuit 17 of the first embodiment described with reference to Figures 1 to 4 is thus deleted.
    Figures 11, 12 and 13 respectively represent the reflection coefficient and the radiation patterns of the antenna 1 according to this second embodiment at a first working frequency of 1575 MHz and at a second working frequency close to 988 MHz.
    The curve 25 in FIG. 11 represents the reflection coefficient of the antenna 1. In FIG. 12, the curve 27 represents its radiation pattern at 1575 MHz according to an RHCP polarization while the curve 28 represents its radiation diagram according to a LHCP polarization. The curve 26 in FIG. 13 represents the radiation diagram of the antenna 1 at 988 MHz according to a vertical rectilinear polarization.
    It should be noted that, unlike the radiation diagrams in FIGS. 7 and 8, the diagrams in FIGS. 12 and 13 present radiation throughout the space, even under the horizontal plane containing the ground plane 11 of the antenna 1 ( 90 ° <Θ <270 °). This is because for the second embodiment, the dimensions of the ground plane 11 are not large enough in front of those of the plate 10 so that it completely reflects the waves emitted by the antenna upwards. On the other hand, if we consider that the antenna was placed on the roof of a motor vehicle, then the roof of the vehicle would play the role of an infinite ground plane, and the radiation observed would be exclusively in the space located above above the ground plane.
    It appears from these different curves that even if the performance of the antenna 1 according to the second embodiment is slightly less good than that of the antenna 1 according to the first embodiment, they remain very satisfactory for the operating modes. expected, namely the reception of GPS signals and the transmission of messages over a loT access network.
    Indeed, at 1575 MHz the antenna has a coefficient Su of around 18 dB and a gain close to 10 dBi in the vertical direction 18 (Θ = 0 °) for the RHCP polarization. In this direction, the gain is -2 dBi for the LHCP polarization. The discrimination of the RHCP polarization with respect to the LHCP polarization is therefore always possible even if the difference in gain between these two polarizations is smaller than for the first embodiment. At 988 MHz, there is a coefficient Su of around -13 dB and a gain close to 2 dBi in the horizontal directions (Θ close to 90 °).
    Figure 14 shows a third embodiment of the antenna 1. In particular, part a) of Figure 14 is a schematic representation of the plate 10 of the antenna 1 for this third embodiment. In this third embodiment, a slot 30 is made in the plate 10 so that it completely surrounds the connection point between the wire 13 returning to ground and the plate 10. A capacitive element 15c then appears: a of its electrodes is formed by the part 10a of the plate 10 which is outside the periphery formed by the slot 30, and its other electrode is formed by the part 10b of the plate 10 which is inside said formed periphery through the slot 30. Thus, instead of using a discrete electronic component 15a or else a metal plate 19, the capacitive element 15c is produced from a slot 30 in the plate 10 at the end of the wire 13 back to ground which is in contact with the plate 10.
    Part b) of FIG. 14 is an enlargement of the particular shape of the slot 30. In the example considered, the slot 30 is inscribed in a side square of length L equal to 10.2 mm, and the thickness of the slot 30 is 0.2 mm. The particular shape of the slot 30 makes it possible to maximize the value of the capacity for a given surface (we sometimes speak in this case of "interdigital capacity"). The dimensions of the slot 30 could vary depending on the dielectric substrate 14 used. Also, it is possible to vary the shape of the slot 30 to obtain different capacity values.
    It is important to note that the capacitive element 15c produced from the slot 30 in this third embodiment distinguishes the antenna 1 from certain wire-plate antennas of the prior art for which slots are also made in the plate . In fact, the slot 30 corresponds to a capacitive element 15c placed in series with the wire 13 returning to ground between the supply wire 12 and the ground plane 11. Thus, unlike the wire-plate antennas of the art previous using slots, for the antenna 1 according to the third embodiment described with reference to FIG. 14 there is no direct electrical connection between the feed wire 12 and the return wire 13 because the slot 30 completely surrounds the connection point between the wire 13 returning to ground and the plate 10.
    FIG. 15 represents the reflection coefficient at the input of the antenna for this third embodiment. There are two resonant frequencies for which the antenna 1 is adapted in impedance. In particular, marker no. 1 indicates the second resonant frequency around 982 MHz and marker no. 2 indicates the first resonant frequency at 1575 MHz.
    The invention also relates to a transmission device comprising an antenna 1 according to any of the embodiments described above and a generator 16 connected to the supply wire 12, adapted to form an electrical signal at the first frequency and / or at the second frequency of work. For example, the generator 16 applies in the supply wire 12 an electric voltage or current at the first working frequency and / or at the second working frequency, thus generating an electromagnetic field radiated by the antenna 1. According to other examples, the transmission device could also include two generators connected to the antenna 1, for example via a duplexer.
    The invention also relates to a reception device comprising an antenna 1 according to any one of the embodiments described above and a receiver connected to the supply wire 12, suitable for receiving an electrical signal at the first working frequency and / or at the second working frequency. For example, the receiver extracts a signal at the first working frequency and / or at the second working frequency from variations in a voltage or an electric current induced in the supply wire 12 by the electric field. an electromagnetic wave picked up by the antenna 1.
    More particularly, the invention relates to a transceiver device comprising an antenna 1 according to any one of the embodiments described above and making it possible to receive, at the first working frequency of the antenna 1, a radio signal comprising geolocation information transmitted by a satellite communication system, and to transmit to a terrestrial wireless communication system, at the second working frequency of the antenna 1, a radioelectric signal comprising the geographical position of said device possibly accompanied by other information.
    These devices include, in conventional manner, one or more microcontrollers, and / or programmable logic circuits (of FPGA, PLD type, etc.), and / or specialized integrated circuits (ASIC), and / or a set of components. discrete electronics, and a set of means, considered to be known to those skilled in the art for signal processing (analog or digital filter, amplifier, analog / digital converter, sampler, modulator, demodulator, oscillator, mixer, etc. .).
    Depending on the embodiment of the antenna 1 chosen, these devices may or may not include an adaptation circuit 17 between the transmission line carrying the radiofrequency signal and the antenna. In particular, for the second embodiment of the antenna 1 described above with reference to FIG. 10, it is possible to do without such an adaptation circuit because the antenna 1, by its very structure, is perfectly adapted in impedance to the two working frequencies considered.
    The above description clearly illustrates that, by its various characteristics and their advantages, the present invention achieves the objectives set. In particular, the antenna 1 according to the invention allows operation at two distinct frequencies according to two different radiation modes and with very satisfactory performance obtained thanks to a good adaptation of impedance to each of the two working frequencies considered. In addition, the invention offers the possibility of easily adjusting at least one of the working frequencies by varying the value of the capacitive element (15a, 15b, 15c). Finally, the mechanical structure of the antenna 1 according to the invention makes it possible to facilitate its manufacture and to reduce its size compared to the solutions of the prior art. The cost of manufacturing such an antenna 1 is also reduced.
    More generally, it should be noted that the embodiments considered above have been described by way of nonlimiting examples, and that other variants are therefore possible. In particular, different working frequencies can be obtained by varying certain parameters of the antenna such as for example the dimensions of the plate 10, the diameter and / or the position of the feed wire 12 and the return wire 13. mass, the value of the dielectric substrate 14, the distance between the plate 10 and the ground plane 11, the value of the capacitive element 15a, 15b, 15c, etc.
    Finally, it should be noted that the invention finds a particularly advantageous application for a device intended to receive signals from GPS satellites and to transmit information to a loT type wireless communication system, but it could have other 5 applications, for example for communication systems using other frequency bands. Also, nothing would prevent a device using an antenna 1 according to the invention from being configured to transmit and receive on each of the two working frequencies of the antenna.
    权利要求:
    Claims (12)
    [1" id="c-fr-0001]
    1. Antenna (1) comprising a ground plane (11), a metal plate (10) arranged opposite said ground plane (11), a supply wire (12) making it possible to connect said plate (10) to a generator (16) or a receiver, so that the antenna (1) has a resonant frequency in plated antenna mode, called “first working frequency”, said antenna (1) being characterized in that it comprises in addition to a ground return wire (13) connecting the plate (10) to the ground plane (11), and a capacitive element (15a, 15b, 15c) arranged in series with the ground return wire (13) between the supply wire (12) and the ground plane (11), so that the antenna (1) also has a resonance frequency in wire-plate antenna mode, called “second working frequency”, lower than said first working frequency.
    [2" id="c-fr-0002]
    2. Antenna (1) according to claim 1 in which the plate (10) is a rectangular plate whose two opposite angles of the same diagonal are truncated so that the antenna (1) has a circular polarization at said first frequency of job.
    [3" id="c-fr-0003]
    3. Antenna (1) according to one of claims 1 or 2 in which the capacitive element (15a) is a discrete electronic component.
    [4" id="c-fr-0004]
    4. Antenna (1) according to claim 3 wherein the capacitive component (15a) is of controllable capacitive value.
    [5" id="c-fr-0005]
    5. Antenna (1) according to one of claims 1 or 2 in which the capacitive element (15b) comprises two electrodes, one of which is formed by a metal plate (19) located at one end of the return wire (13) to ground and arranged opposite the plate (10) of the antenna (1) or the ground plane (11).
    [6" id="c-fr-0006]
    6. Antenna (1) according to claim 5 wherein said metal plate (19) of the capacitive element (15b) is located at the end of the wire (13) for return to ground on the side of the plate (10) of the antenna (1), so that the other electrode is formed by the plate (10) of the antenna (1).
    [7" id="c-fr-0007]
    7. Antenna (1) according to one of claims 1 or 2 in which a slot (30) is made in the plate (10) so that said slot (30) completely surrounds the connection point between the wire (13 ) back to ground and the plate (10), and the capacitive element (15c) comprises two electrodes, one electrode of which is formed by a part (10a) of the plate (10) which is outside of a periphery formed by the slot (30), and the other electrode is formed by another part (10b) of the plate (10) which is inside said periphery formed by the slot (30).
    [8" id="c-fr-0008]
    8. Antenna (1) according to one of the preceding claims in which at least one of the ground return (13) and supply (12) wires is a metal strip cut from the plate (10).
    [9" id="c-fr-0009]
    9. Antenna (1) according to one of the preceding claims in which the distance between the feed wire (12) and the return ground wire (13) is greater than one tenth of the wavelength of the second working frequency.
    [10" id="c-fr-0010]
    10. Transmission device comprising an antenna (1) according to one of claims 1 to 9 and a generator (16) connected to the supply wire (12), adapted to form an electrical signal at the first working frequency and / or at the second working frequency.
    [11" id="c-fr-0011]
    11. Reception device comprising an antenna (1) according to one of claims 1 to 9 and a receiver connected to the supply wire (12), adapted to receive an electrical signal at the first working frequency and / or at the second working frequency.
    [12" id="c-fr-0012]
    12. A transceiver device comprising an antenna (1) according to one of claims 1 to 9 configured to receive a signal at the first working frequency comprising geolocation information transmitted by a satellite communication system and to transmit to a 5 terrestrial wireless communication system a signal at the second working frequency comprising the geographical position of said device.
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    同族专利:
    公开号 | 公开日
    WO2019034760A1|2019-02-21|
    EP3669422A1|2020-06-24|
    US11196162B2|2021-12-07|
    FR3070224B1|2020-10-16|
    US20200227829A1|2020-07-16|
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    法律状态:
    2019-02-22| PLSC| Publication of the preliminary search report|Effective date: 20190222 |
    2019-08-29| PLFP| Fee payment|Year of fee payment: 3 |
    2020-08-28| PLFP| Fee payment|Year of fee payment: 4 |
    2021-08-30| PLFP| Fee payment|Year of fee payment: 5 |
    优先权:
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