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    • 专利摘要:
    The invention relates to a reversible DC-DC converter comprising: a first field effect transistor (S1) and a second field effect transistor (S2) in series between a first terminal (11) and a second terminal (12) a DC voltage (Vdc); an inductive element (L1) connecting a first midpoint (13) of the series connection of the two transistors to a first terminal (15) of an alternating voltage (Vac); a first triac (T1) and a second triac (T2) in series between the DC voltage terminals, a second midpoint (17) of the series association of the two triacs being connected to a second terminal (16) of the voltage alternative.
    公开号:FR3068546A1
    申请号:FR1756179
    申请日:2017-06-30
    公开日:2019-01-04
    发明作者:Ghafour Benabdelaziz；Cedric REYMOND；David Jouve
    申请人:STMicroelectronics Tours SAS；
    IPC主号:
    专利说明:

    REVERSIBLE AC / DC CONVERTER TO TRIACS
    Field
    The present application relates generally to electronic circuits and, more particularly, to switching converters known as pole totem output, or mid-point cascode.
    Presentation of the prior art
    Switching converters are used in many applications and many types of converters are known.
    Among the AC-DC converters, there are many architectures with rectifying bridges and other architectures without bridges, based on the switching of two transistors (generally MOS) mounted in cascode at mid point (pole totem).
    These converters are generally used for their efficiency in correcting the power factor (Power Factor Corrector - PFC).
    summary
    There is a need to improve pole totem converters.
    One embodiment proposes a reversible pole totem converter architecture.
    B16203 - 17-TO-0342
    One embodiment offers a solution compatible with a limitation of the inrush current.
    Thus, one embodiment provides for a reversible AC-DC converter, comprising:
    a first field effect transistor and a second field effect transistor in series between a first terminal and a second terminal for DC voltage;
    an inductive element connecting a first midpoint of the association in series of the two transistors to a first terminal intended for an alternating voltage; and a first triac and a second triac in series between the DC voltage terminals, a second midpoint of the series association of the two triacs being connected to a second terminal intended for the AC voltage.
    According to one embodiment:
    a first diode is in parallel with the first transistor, anode on the first midpoint side; and a second diode is in parallel with the second transistor, cathode on the first midpoint side.
    According to one embodiment, each diode is defined by the intrinsic drain-source diode of the transistor concerned.
    According to one embodiment, a trigger of each triac is on the second mid-point side.
    According to one embodiment, a trigger of each triac is on the side of the terminal of the DC voltage to which the triac concerned is connected.
    According to one embodiment:
    a trigger of the first triac is on the second mid-point side; and a trigger of the second triac is on the second DC terminal side.
    One embodiment provides a method for controlling a converter, in which:
    B16203 - 17-TO-0342 the second triac is made to pass continuously during half-waves of a first sign of the alternating voltage; and the first triac is made passing continuously during half-waves of a second sign of the alternating voltage.
    According to one embodiment, in an alternative-continuous conversion mode:
    the second transistor is impulse-controlled during the alternations of the first sign; and the first transistor is driven impulsively during the alternations of the second sign.
    According to one embodiment, the first diode serves as a freewheeling diode.
    According to one embodiment, in a continuous-alternative conversion mode:
    the first transistor is impulse-controlled during the alternations of the first sign; and the second transistor is driven impulsively during the alternations of the second sign.
    According to one embodiment, the second diode serves as a freewheeling diode.
    Brief description of the drawings
    These characteristics and advantages, as well as others, will be explained in detail in the following description of particular embodiments made without implied limitation in relation to the attached figures, among which:
    FIG. 1 is an electrical diagram of a usual example of a totem alternating-DC pole converter;
    Figure 2 shows, schematically and partially, partly in the form of blocks, an embodiment of a totem reversible pole converter;
    FIGS. 3A, 3B, 3C, 3D, 3E, 3F, 3G and 3H illustrate, in the form of timing diagrams, the operation of the converter of FIG. 2 in AC-DC conversion mode;
    B16203 - 17-TO-0342 FIGS. 4A, 4B, 4C, 4D, 4E, 4F, 4G and 4H illustrate, in the form of timing diagrams, the operation of the converter of FIG. 2 in continuous-AC conversion mode;
    FIG. 5 represents, in more detail, an embodiment of the reversible pole totem converter of FIG. 2;
    FIG. 6 shows, schematically and partially in the form of blocks, another embodiment of a totem reversible pole converter;
    FIG. 7 represents, schematically and partially in the form of blocks, another embodiment of a totem reversible pole converter; and FIG. 8 represents, schematically and partially in the form of blocks, an embodiment of a circuit for generating direct voltages of control circuits of a reversible pole totem converter.
    detailed description
    The same elements have been designated by the same references in the different figures. In particular, the structural and / or functional elements common to the various embodiments may have the same references and may have identical structural, dimensional and material properties.
    For the sake of clarity, only the steps and elements useful for understanding the embodiments which will be described have been shown and will be detailed. In particular, the final application of the converter has not been detailed, the embodiments described being compatible with the usual applications of AC-DC, DC-AC or reversible converters.
    Unless otherwise specified, when reference is made to two elements connected to each other, this means directly connected without any intermediate element other than conductors, and when reference is made to two elements connected to each other, it means that these two elements can be directly
    B16203 - 17-TO-0342 connected (connected) or connected via one or more other elements.
    In the description which follows, the expressions approximately, substantially, and of the order of mean to the nearest 10%, preferably to the nearest 5%.
    Figure 1 is an electrical diagram of a common example of pole-to-pole, AC-to-DC converter.
    A pole totem converter is based on the use of two MOS transistors (here in N channel) SI and S2, connected in series between two terminals 11 and 12 for supplying a DC voltage Vdc. The drain of transistor SI is on terminal 11 and the source of transistor S2 is on terminal 12. A storage element Cl (capacitor or battery for example) of continuous energy connects terminals 11 and 12, terminal 11 being, arbitrarily , the positive terminal of the voltage Vdc. The midpoint 13 between the two transistors SI and S2 is connected, by means of an inductive element L1 in series with a circuit 14 for limiting the inrush current and losses in steady state, to a first terminal 15 d application of an alternating voltage Vac. The circuit 14 is, for example, a resistor R (with positive temperature coefficient PTC or negative NTC) in parallel with a switch K. The resistor R limits the inrush current at start-up and the switch K short-circuits the resistor in steady state to limit resistive losses once the voltage balance is reached. A second terminal 16 for applying the alternating voltage Vac is connected to the midpoint 17 of a series association of two diodes D3 and D4 connected between the terminals 11 and 12. The anodes of the diodes D3 and D4 are respectively on point 17 and terminal 12 side.
    In practice, the terminals 15 and 16 correspond to terminals for connection to the electrical distribution network and an input filter 18 (FILTER), or mains filter, is interposed between on the one hand the terminal 15 and the circuit 14 and, on the other hand, terminal 16 and point 17. An element 19 for measuring the alternating current is inserted between the filter 18 and point 17.
    B16203 - 17-TO-0342
    The information representative of the current, measured by the element 19, is used by a control circuit 20 (CTRL) for the conduction periods of the transistors SI and S2. The circuit 20 receives other information such as, for example, information representative of the voltage Vdc, information representative of the energy requirements of the load connected to the terminals 11 and 12, etc. The circuit 20 supplies control signals to circuits (DRIVER) 21 and 22 for generating control signals from the gates of the respective transistors SI and S2. In FIG. 1, the intrinsic source-drain diodes DI and D2 of the transistors SI and S2 have also been shown. The transistors SI and S2 are controlled in pulse width modulation according to the needs of the load connected to terminals 11 and 12. The frequency of the pulses is generally fixed and is clearly higher (ratio of at least 100, for example of a few kHz to a few hundred kHz) at the frequency of the Vac voltage (generally less than 100 Hz, typically 50 Hz or 60 Hz for the electricity distribution network).
    The operation of the totem pole converter in FIG. 1 is as follows. To simplify, the presence of the filter 18 is not taken into account, but it is of course crossed by the current from the terminals 15 and 16 and towards these terminals.
    During the positive alternations of the voltage Vac, the transistor S2 is controlled by pulse width modulation in order to be periodically closed (passing) and the transistor SI remains permanently open (blocked). Furthermore, the source-drain diode D2 of the transistor S2 is reverse biased while the source-drain diode DI of the transistor SI is directly biased and serves as a freewheeling diode. During the closing pulses of transistor S2, inductance L1 accumulates energy. The current flows from terminal 15 via inductance Ll, transistor S2 and diode D4 to terminal 16. The continuous load connected to terminals 11 and 12 is supplied by the energy stored in the energy storage element Cl (capacitor or battery). Each time transistor S2 is opened,
    B16203 - 17-TO-0342 the energy stored in the inductor L1 is transferred to the continuous load. The current is then circulated from the inductance Ll, via the diode DI of the transistor SI to the positive terminal 11, then from the negative terminal 12, via the diode D4 to the terminal 16 to loop back to the inductance Ll. In some cases, the diode DI is a diode in parallel on the transistor SI.
    During the negative alternations of the voltage Vac, the transistor SI is controlled by pulse width modulation to be periodically closed (on) and the transistor S2 remains permanently open (blocked). Furthermore, the source-drain diode DI of the transistor SI is reverse biased while the source-drain diode D2 of the transistor S2 is directly biased and serves as a freewheeling diode. During the closing pulses of the transistor SI, the inductance L1 accumulates energy. Current is circulated from terminal 16 via diode D3, transistor SI and inductance Ll to terminal
    15. The continuous load connected to terminals 11 and 12 is supplied by the energy stored in the energy storage element Cl. Each time the transistor S2 is opened, the energy stored in the inductance Ll is transferred to the load keep on going. The current is then circulated from the inductance Ll, via terminals 15 then 16, the diode D3, to the positive terminal 11, then from the negative terminal 12, via the diode D2 to the inductance ll.
    The inrush current limiting circuit 14 is used before each closing pulse of one of the transistors SI and S2, in particular when one moves away from the voltage zero of the voltage Vac. Indeed, the voltage across the transistor SI or S2 when it is closed is all the more important as one is close to the middle of the corresponding alternation, which, without limitation circuit, would cause a current peak. The opening of the switch K, in an impulse manner, before each start of the closing pulse of the transistors SI and S2 so that the resistor R limits the charging current of the capacitor Cl, avoids
    B16203 - 17-TO-0342 these peaks of current, in particular towards the middle of each alternation.
    The converter in FIG. 1 is unidirectional, that is to say that it can only operate in an AC-DC converter (rectifier or rectify mode). In certain applications, it is desired to have a reversible converter, that is to say capable of also functioning as a DC-AC converter. This is used, for example, to re-inject energy into the electrical distribution network or to power a motor from a battery. The converter must then be able to operate as an inverter.
    The described embodiments plan to take advantage of the advantages of a pole-totem architecture and of its efficiency to produce a reversible converter.
    An example of application of a reversible converter is to allow, with the same converter, both to supply a load from the electrical distribution network and to inject energy on the network when the load does not consume not.
    Another example of application of a reversible converter is to allow, with the same converter, both to power a motor (transfer of electrical-mechanical energy) from a battery and to recharge the battery (transfer mechanical-electrical energy) from the motor rotation.
    One could think of using MOS transistors in place of diodes D3 and D4 in order to make the structure bidirectional. However, the need to limit the inrush current makes this solution very restrictive in terms of controlling the MOS transistors and the size and reliability of the circuit for limiting losses in steady state. The circuit 14 for limiting the inrush current is moreover essential.
    One could also think of using thyristors instead of diodes D3 and D4. However, this would not be enough to make the converter bidirectional.
    B16203 - 17-TO-0342
    Figure 2 shows, schematically and partially, partly in the form of blocks, an embodiment of a totem pole reversible converter.
    We find a pole totem structure of two field effect transistors SI and S2, for example MOS transistors (here with N channel), connected in series between two terminals 11 and 12 with a DC voltage Vdc. The drain of transistor SI is on terminal 11 and the source of transistor S2 is on terminal 12. A storage element Cl (capacitor or battery for example) of continuous energy connects terminals 11 and 12, terminal 11 being, arbitrarily , the positive terminal of the voltage Vdc.
    The midpoint 13 between the two transistors SI and S2 is connected, via an inductive element L1, to a first terminal 15 of an alternating voltage Vac. According to the embodiments described, provision is made to replace the diodes D3 and D4 of FIG. 1 with triacs. Thus, a second terminal 16 of the alternating voltage Vac is connected to the midpoint 17 of a series association of two triacs Tl and T2 connected between terminals 11 and 12. In the example of FIG. 2, the triggers gTl and GT2 of triacs Tl and T2 are respectively on terminal 11 and terminal 12.
    As will be seen below, thanks to the proposed solution, a circuit for limiting the inrush current (14, FIG.
    1) is not necessary.
    The terminals 15 and 16 correspond for example to terminals for connection to the electrical distribution network or to the terminals of a motor, etc., and an input filter 18 (FILTER), or mains filter, is preferably inserted between d firstly the terminal 15 and the node 13 and secondly the terminal 16 and the point 17. An element 19 for measuring the alternating current is inserted between the filter 18 and the point 17. The information representative of the current , measured by the element 19, is used by a control circuit 20 (CTRL) for the conduction periods of the transistors SI and S2 and of the triacs Tl and T2. The circuit 20 receives other information such as, for example, information
    B16203 - 17-TO-0342 representative of the voltage Vdc, information representative, in rectifier mode, of the needs of the continuous load connected to terminals 11 and 12, etc. Circuit 20 supplies control signals to circuits (DRIVER) 21 and 22 for generating control signals from gates gSl and gS2 of the respective transistors SI and S2 as well as, directly or indirectly, control signals to the triggers gTl and gT2 Tl and T2 triacs. FIG. 2 also shows the intrinsic source-drain diodes DI and D2 of the transistors SI and S2. As a variant, the diodes DI and D2 can be additional components. According to another variant, the transistor S1 or S2 is turned on during the periods when the current must flow in the diode Dl, respectively D2. This makes it possible to reduce the conduction losses compared to a current flow in the intrinsic diode Dl or D2. The transistors SI and S2 are controlled by pulse width modulation. The pulse frequency is generally fixed and is clearly higher (ratio of at least 100, for example from a few kHz to a few hundred kHz) than the frequency of the voltage Vac (generally less than 100 Hz, typically 50 Hz or 60 Hz for the electricity distribution network). The converter does not raise or lower the voltage in one direction or another. We are concerned here only with continuous alternating conversion and vice versa. If necessary, other conversion and regulation systems are present upstream or downstream to achieve a decrease or an increase in the values of the voltages Vac and Vdc.
    At first glance, the use of triacs in a pole totem architecture seems unnecessary due to the presence of the transistors SI and S2. However, as is apparent from the embodiments below, the use of two triacs in place of two diodes makes it possible not only to avoid the circuit for limiting the inrush current, but also to make the converter reversible with a particularly simple operation.
    B16203 - 17-TO-0342
    FIGS. 3A, 3B, 3C, 3D, 3E, 3F, 3G and 3H illustrate, in the form of timing diagrams, the operation of the converter of FIG. 2 in AC-DC conversion mode during a period of the AC voltage Vac .
    FIG. 3A shows an example of the shape of the voltage Vac between the terminals 15 and 16 (line or motor voltage). FIG. 3B represents a corresponding example of the shape of the lake current (line current or motor). FIG. 3C represents an example of the corresponding shape of the voltage Vdc between the terminals 11 and 12 (battery or capacitor Cl voltage). FIG. 3D represents a corresponding example of the shape of the current Idc on the DC voltage side. FIG. 3E represents an example of closing periods of the triac T2. FIG. 3F represents an example of the corresponding shape of the gate voltage gS2 of the transistor S2. FIG. 3G represents an example of periods of closure of the triac Tl. FIG. 3H represents an example of the corresponding shape of the gate voltage gSl of the transistor SI.
    We are in steady state, that is to say that we consider that the capacitor C1 is at the charge level required by the application. Start-up operation is similar, but the voltage Vdc gradually increases over several alternations until it reaches its nominal level set by the application. To simplify the explanations, the presence of the filter 18 is neglected in the following.
    In AC-DC conversion mode, the triac T2 is turned on during the positive half-waves of the voltage Vac while the triac Tl is turned on during the negative half-waves of the alternating voltage. However, unlike the diodes D3 and D4 of the classic case of FIG. 1, the conduction of the triacs Tl and T2 does not depend on the conduction periods of the transistors SI and S2, but is forced during the maximum of the possible duration positive and negative alternations. This duration covers at least the entire duration of the pulse train for controlling the transistors S1 and S2, and is fixed by the half-period of the alternating voltage. So closing
    B16203 - 17-TO-0342 of the transistor SI or S2 (depending on the alternation of the voltage Vac) takes place when the voltage across its terminals is approximately zero. The control of the transistors SI and S2 is not modified by the embodiments described. Note that a triac crashes, if there is no control, when the current flowing through it cancels (becomes less than its holding current). Thus, due to the discontinuity of the current during each alternation, in order to avoid an inadvertent blocking of the triac Tl or T2, the control is maintained for approximately the entire duration of an alternation (negative for the triac Tl and positive for the triac T2). The order of the triac concerned is interrupted at the end of the alternation.
    During the positive alternations of the voltage Vac, the transistor S2 is controlled by pulse width modulation in order to be periodically closed (passing) and the transistor SI remains permanently open (blocked). Furthermore, the source-drain diode D2 of the transistor S2 is reverse biased while the source-drain diode DI of the transistor SI is directly biased and serves as a freewheeling diode. During the closing pulses of transistor S2, inductance L1 accumulates energy. Current is circulated from terminal 15 via inductance Ll, transistor S2 and triac T2 to terminal
    16. The continuous load connected to terminals 11 and 12 is supplied by the energy stored in the energy storage element C1 (capacitor or battery). At each opening of the transistor S2, the energy stored in the inductance L1 is transferred to the continuous load. The current is then circulated from the inductance Ll, via the diode DI of the transistor SI to the positive terminal 11, then from the negative terminal 12, via the triac T2 to the terminal 16 to loop back to the inductance Ll.
    During the negative alternations of the voltage Vac, the transistor SI is controlled by pulse width modulation to be periodically closed (on) and the transistor S2 remains permanently open (blocked). Furthermore, the source-drain diode DI of the transistor SI is reverse biased while the
    B16203 - 17-TO-0342 source-drain diode D2 of transistor S2 is directly biased and serves as a freewheeling diode. During the closing pulses of the transistor SI, the inductance L1 accumulates energy. The current flows from terminal 16 via the triac Tl, the transistor SI and the inductance L1 to the terminal
    15. The continuous load connected to terminals 11 and 12 is supplied by the energy stored in the energy storage element Cl. Each time the transistor S2 is opened, the energy stored in the inductor L1 is transferred to the load keep on going. The current is then circulated from the inductance Ll, via terminals 15 then 16, the triac Tl, to the positive terminal 11, then from the negative terminal 12, via the diode D2 to the inductance ll.
    The use of triacs Tl and T2 has another advantage which is to allow operation in an inverter, that is to say in DC-AC conversion. We take advantage here of the fact that the triacs are bidirectional.
    FIGS. 4A, 4B, 4C, 4D, 4E, 4F, 4G and 4H illustrate, in the form of timing diagrams, the operation of the converter of FIG. 2 in DC-AC conversion mode during a period of the AC voltage Vac .
    FIG. 4A represents an example of the shape of the voltage Vac between the terminals 15 and 16 (line or motor voltage). FIG. 4B represents a corresponding example of the shape of the lake current (line current or motor). FIG. 4C shows an example of the corresponding shape of the voltage Vdc between the terminals 11 and 12 (battery or capacitor Cl voltage). FIG. 4D represents a corresponding example of the shape of the current Idc on the DC voltage side. FIG. 4E represents an example of the closure periods of the triac T2. FIG. 4F shows an example of the corresponding shape of the gate voltage gS2 of the transistor S2. FIG. 4G represents an example of periods of closure of the triac Tl. FIG. 4H represents an example of the corresponding shape of the gate voltage gSl of the transistor SI.
    B16203 - 17-TO-0342
    In inverter mode, the question of the established regime of the voltage Vdc does not arise. Indeed, it is a question here of transferring energy from the continuous source (charged battery for example) to the alternative load.
    To operate as an inverter, that is to say for example reinjecting energy into the electrical distribution network or supplying a motor, the direction of current flow in the converter must be reversed compared to the case of the AC converter. continued. Thus, with the same sign conventions, the current Idc is always negative. Furthermore, the sign of the lac current is reversed with respect to the sign of the voltage Vac, that is to say that it is negative during the positive half-waves and positive during the negative half-waves.
    As in the rectifier mode, the triac T2 is turned on continuously during the positive half-waves of the alternating voltage Vac while the triac Tl is turned on continuously during the negative half-waves of the alternating voltage Vac. However, on the transistors SI and S2 side, unlike the rectifier mode, the transistor SI is controlled during the positive half-waves and the transistor S2 is controlled during the negative half-waves of the voltage Vac. The transistors SI and S2 are always controlled, on a pulse basis, preferably in pulse width modulation if the alternating load is likely to vary (for example in the case of a motor).
    During the positive alternations of the voltage Vac, the transistor SI is controlled by pulse width modulation to be periodically closed (on) and the transistor S2 remains permanently open (blocked). Furthermore, the source-drain diode DI of the transistor SI is reverse biased while the source-drain diode D2 of the transistor S2 is directly biased and serves as a freewheeling diode. During the closing pulses of the transistor SI, the inductance L1 accumulates energy. The current flows from terminal 11 via the
    B16203 - 17-TO-0342 transistor SI and inductance L1 up to terminal 15, then from terminal 16, via triac T2 to terminal 12. Each time the transistor IS is opened, the energy stored in inductance L1 is transferred to the AC network (or to the motor). The current is then circulated from the inductor L1 to terminal 15, then from terminal 16, via the triac T2 and the diode D2 to the inductor L1.
    During the negative half-waves of the voltage Vac, the transistor S2 is controlled by pulse width modulation in order to be periodically closed (on) and the transistor SI remains permanently open (blocked). Furthermore, the source-drain diode D2 of the transistor S2 is reverse biased while the source-drain diode DI of the transistor SI is directly biased and serves as a freewheeling diode. During the closing pulses of transistor S2, inductance L1 accumulates energy. The current is circulated from terminal 11, via the triac Tl to terminal 16, then from terminal 15, via the inductor L1 and the transistor S2 to terminal 12. At each opening of the transistor S2, the energy stored in inductance L1 is transferred to the alternating network. The current is then circulated from the inductor L1, via the diode Dl, the triac Tl up to terminal 16, is looped back through terminal 15 into the inductor L1.
    With respect to the rectifier mode, care is taken at each end of alternation to stop the control pulses of the transistors SI and S2 sufficiently early to guarantee that the lac current is zero at the end of the alternation.
    The applications more particularly targeted are applications in which the voltages Vac and Vdc have amplitudes greater than 100 volts. However, the control signals of the transistors SI and S2 and of the triacs Tl and T2 have amplitudes ranging from a few volts to 10-20 volts. Consequently, it is necessary to provide circuits for generating these control signals having appropriate voltage references.
    B16203 - 17-TO-0342
    The following figures show the supply connections and potentials required for the control signals of the transistors and triacs in different embodiments.
    FIG. 5 represents, in more detail, an embodiment of the reversible pole totem converter of FIG.
    2.
    On the transistor S2 side, its source being ground GND (potential of terminal 12), the reference potential of its gate control signal gS2 can also be ground GND. Circuit 22 is, for example, supplied by a positive voltage 15VDC (terminal 51), of 15 volts, referenced to earth GND and receives a low voltage digital signal CTRLS2 (of a few volts, for example 3-5 volts) from the circuit 20 (for example, a microcontroller).
    On the transistor SI side, the voltage of terminal 11 is too high to authorize a command gS1 referenced to ground GND. In the example of FIG. 5, provision is made to reference the supply voltage, for example 15 volts, from circuit 21 to node 13. As node 13 corresponds to the source of transistor SI, this guarantees a gate voltage- positive source whatever the potential of node 13 (which evolves with voltage Vac). A 15VDC potential of 15 volts (referenced to GND ground) is applied to the anode of a diode D5 whose cathode is connected to a terminal 52 for applying the positive supply potential of the circuit
    21. A terminal 53 for applying the reference potential of circuit 21 is connected to node 13. A capacitor C2 connects the cathode of diode D5 to node 13 to adapt the reference of the 15-volt voltage supplying circuit 21. By due to the change in voltage reference, a low voltage control signal CTRLS1, supplied by the circuit 20, is applied via an optocoupler 54 (Opto) whose conduction terminals (the phototransistor transmitter and collector bipolar output) are respectively connected to terminal 52 and to an input control terminal of circuit 21. The signal CTRLS1
    B16203 - 17-TO-0342 is applied to the control terminal of the optocoupler (the anode of its photodiode) by being referenced to GND ground.
    On the triac Tl side, a triac Tl trigger current is injected by the transistor of an optocoupler 55 (Opto) whose conduction terminals (emitter and collector of the phototransistor) are connected to an electrode of a capacitor C82 defining a floating mass GNT_T of a continuous supply (for example, of the order of 15 volts) isolated (floating) and, by a resistor RI, at the trigger of the triac Tl. Another electrode of the capacitor C82 is connected to a terminal 56 of application of the floating positive potential VDC_T of the isolated continuous supply referenced to the potential GND_T. In the example of FIG. 5, the terminals 11 and 56 are combined. The trigger current is therefore extracted from the triac Tl. As a variant, the terminals VDC_T and GND_T are inverted and the trigger current is injected into the triac Tl. A low voltage control signal CTRLT1, supplied by the circuit 20, is applied to the control terminal of the optocoupler 55 (the anode of its photodiode) by being referenced to GND ground.
    On the triac side T2, one of the electrodes of which is connected to ground GND, a trigger current can be injected directly from circuit 20 by application of a low voltage control signal CTRLT2, via a resistor R2.
    FIG. 6 schematically and partially in the form of blocks, another embodiment of a reversible pole totem converter.
    Compared to the diagram in FIG. 5, the triggers of the triacs T1 and T2 are on point 17.
    Two optocouplers 57 and 58 (Opto) are then used, the respective control terminals (photodiodes) of which receive the low voltage signals CTRLT1 and CTRLT2 supplied by the circuit 20 (not shown in FIG. 6) and referenced to GND ground.
    In the example of FIG. 6, it is assumed that one wishes to extract the trigger currents from the triacs T1 and T2. The conduction terminals (the emitter and the collector of the phototransistor) of the optocouplers 57 and 58 are respectively
    B16203 - 17-TO-0342 connected, via resistors RI and R2, to the triggers of the triacs Tl and T2 and to a terminal 56 for applying the floating mass GND_T of the isolated continuous supply. In this embodiment, the floating positive potential VDC_T (for example, of the order of 15 volts) corresponds to the potential of point 17, the capacitor C82 connecting point 17 and terminal 56. The rest of the assembly is identical to that of figure 5.
    As a variant, the relationship between the potentials of terminals 56 (VDC_T) and 17 (GND_T) is reversed and the trigger currents of the triacs T1 and T2 are injected into the triggers instead of being extracted from the triggers.
    FIG. 7 shows, schematically and partially in the form of blocks, another embodiment of a reversible pole totem converter.
    Compared to the embodiment of FIG. 6, the trigger of the triac T2 is on terminal 12 side (as in FIG. 5). The CTRLT2 signal can therefore be applied directly to it.
    FIG. 8 schematically and partially in the form of blocks, an embodiment of a circuit for generating direct voltages of control circuits of a reversible pole totem converter.
    This figure illustrates an example of an assembly for generating potentials VDC_T, GND_T and 15VDC from the alternating voltage Vac.
    A transformer 81 with two secondary windings 82 and 83 is used. A primary winding 84 of the transformer is connected, if necessary by means of the filter 18 (FIG.
    2), between terminal 15 (FIG. 2) and a terminal of a switching converter 85 (CONV), for example an integrated circuit known under the trade name VIPER, the other terminal of which is connected, where appropriate by l filter 18 (figure 2), to terminal 16 (figure 2).
    The first secondary winding 82 of the transformer 81 provides the floating voltage (for example of the order of 15 volts) VDC_T-GND_T. For this, a first terminal of the winding
    B16203 - 17-TO-0342 defines the potential GND_T and is connected to the optocoupler 55 in the embodiment of FIG. 5 or to terminal 56 in the embodiments of FIGS. 6 and 7. A second terminal of the winding 82 is connected at the input (anode) of a rectifying element D82 (for example, a diode) and a capacitor C82 connects the two terminals of winding 82. The output (cathode) of the rectifying element D82 defines the potential VDC_T and is connected to terminal 56 in the embodiment of FIG. 5 or to point 17 in the embodiments of FIGS. 6 and 7.
    The second secondary winding 83 of the transformer supplies the voltage 15VDC-GND. For this, a first terminal of the winding 83 defines the potential GND and is connected to the terminal 12 (Figures 5 to 7). A second terminal of the winding 83 is connected at the input (anode) of a rectifying element D83 (for example, a diode) and a capacitor C83 connects the two terminals of the winding 83. The output (cathode) of the 'rectifier D83 defines the potential 15VDC and is connected to terminal 51 (Figures 5 to 7).
    The amplitudes of the voltages VDC_T-GND_T and 15VDC-GND depend on the transformation ratios of the windings 82 and with respect to the winding 84.
    The voltage 15VDC-GND can be used to generate the low voltage (for example, 3.3 volts) referenced to ground GND for the circuit or microcontroller 20. For this, we use, for example, a linear regulator 87 (REG) .
    An advantage of the embodiments described is that the totem pole converter thus produced is particularly efficient. In particular, it obviates the need for a circuit for limiting the inrush current, while obtaining a reversible converter.
    Particular embodiments have been described. Various variants and modifications will appear to those skilled in the art. In particular, the choice of assembly among those of FIGS. 5 to 7 depends on the application and on the circuit used to generate the control voltages. Indeed, the circuit of figure 8
    B16203 - 17-TO-0342 is only an example and we can alternatively use voltages present in the rest of the application. In addition, the practical implementation of the embodiments and the dimensioning of the components is within the reach of those skilled in the art from the functional description given above.
    权利要求:
    Claims (11)
    [1" id="c-fr-0001]
    1. Reversible AC-DC converter, comprising:
    a first field effect transistor (SI) and a second field effect transistor (S2) in series between a first terminal (11) and a second terminal (12) for DC voltage (Vdc);
    an inductive element (L1) connecting a first midpoint (13) of the series association of the two transistors to a first terminal (15) intended for an alternating voltage (Vac); and a first triac (Tl) and a second triac (T2) in series between the DC voltage terminals, a second midpoint (17) of the series association of the two triacs being connected to a second terminal (16) intended for alternating voltage.
    [2" id="c-fr-0002]
    2. Converter according to claim 1, in which:
    a first diode (Dl) is in parallel with the first transistor (SI), anode on the side of the first midpoint (13); and a second diode (D2) is in parallel with the second transistor (S2), cathode on the side of the first midpoint (13).
    [3" id="c-fr-0003]
    3. Converter according to claim 2, wherein each diode (Dl, D2) is defined by the intrinsic drainsource diode of the transistor (SI, S2) concerned.
    [4" id="c-fr-0004]
    4. Converter according to any one of claims 1 to 3, in which a trigger of each triac (Tl, T2) is on the second mid-point side (17).
    [5" id="c-fr-0005]
    5. Converter according to any one of claims 1 to 3, in which a trigger of each triac (Tl, T2) is on the side of the terminal (11, 12) of the direct voltage (Vdc) to which the triac is connected concerned.
    [6" id="c-fr-0006]
    6. Converter according to any one of claims 1 to 3, in which:
    a trigger of the first triac (Tl) is on the second mid-point side (17); and
    B16203 - 17-TO-0342 a trigger for the second triac (T2) is on the second terminal (12) of direct voltage (Vdc) side.
    [7" id="c-fr-0007]
    7. Method for controlling a converter according to any one of claims 1 to 6, in which:
    the second triac (T2) is turned on continuously during half-waves of a first sign of the alternating voltage (Vac); and the first triac (Tl) is made passing continuously during alternations of a second sign of the alternating voltage.
    [8" id="c-fr-0008]
    8. The method as claimed in claim 7, in which, in an alternating-continuous conversion mode:
    the second transistor (S2) is impulse-controlled during the alternations of the first sign; and the first transistor (SI) is impulse-controlled during the alternations of the second sign.
    [9" id="c-fr-0009]
    9. The method of claim 8, in connection with claim 2 or 3, wherein the first diode (Dl) serves as a freewheeling diode.
    [10" id="c-fr-0010]
    10. Method according to any one of claims 7 to 9, in which, in a continuous-alternative conversion mode:
    the first transistor (SI) is impulse-controlled during the alternations of the first sign; and the second transistor (S2) is pulsed controlled during the alternations of the second sign.
    [11" id="c-fr-0011]
    11. The method of claim 10, in connection with claim 2 or 3, wherein the second diode (D2) serves as a freewheeling diode.
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    同族专利:
    公开号 | 公开日
    EP3422555A1|2019-01-02|
    CN109217708A|2019-01-15|
    CN109217708B|2021-11-16|
    US20190006960A1|2019-01-03|
    FR3068546B1|2020-12-11|
    EP3422555B1|2021-08-04|
    CN208589931U|2019-03-08|
    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    WO2017122519A1|2016-01-12|2017-07-20|住友電気工業株式会社|Power conversion device and control method for power conversion device|
    AU500600B2|1974-03-27|1979-05-24|Borg-Warner Corporation|Bipolar inverter circuits|
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    EP3349343B1|2013-11-08|2019-07-17|Delta Electronics Public Co., Ltd.|Resistorless precharging|
    FR3034924A1|2015-04-07|2016-10-14|Stmicroelectronics Sas|ALTERNATIVE-CONTINUOUS CONVERTER WITH CURRENT CURRENT LIMITATION|
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    FR3068546B1|2017-06-30|2020-12-11|St Microelectronics Tours Sas|REVERSIBLE AC / DC CONVERTER TO TRIACS|FR3068546B1|2017-06-30|2020-12-11|St Microelectronics Tours Sas|REVERSIBLE AC / DC CONVERTER TO TRIACS|
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    法律状态:
    2019-01-04| PLSC| Publication of the preliminary search report|Effective date: 20190104 |
    2020-05-20| PLFP| Fee payment|Year of fee payment: 4 |
    优先权:
    申请号 | 申请日 | 专利标题
    FR1756179A|FR3068546B1|2017-06-30|2017-06-30|REVERSIBLE AC / DC CONVERTER TO TRIACS|
    FR1756179|2017-06-30|FR1756179A| FR3068546B1|2017-06-30|2017-06-30|REVERSIBLE AC / DC CONVERTER TO TRIACS|
    EP18178861.3A| EP3422555B1|2017-06-30|2018-06-20|Reversible ac/dc converter with triacs|
    US16/020,413| US20190006960A1|2017-06-30|2018-06-27|Reversible ac-dc and dc-ac triac converter|
    CN201821040019.9U| CN208589931U|2017-06-30|2018-06-29|Reversible transducer|
    CN201810717308.6A| CN109217708B|2017-06-30|2018-06-29|Reversible AC-DC and DC-AC triac converter|
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