• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    Flux-gate current sensor comprising an excitation winding (13), an excitation module (20) for generating an excitation voltage (Ve), a measuring winding (14) in which an induced current flows measurement device (Iim), a synchronous measurement demodulator (22) for multiplying the measurement induced current by a frequency demodulation signal 2.f0 to obtain an image voltage of the current to be measured. The excitation voltage (Ve) is obtained from a first frequency voltage f0 and a second frequency voltage 3.f0, the fluxgate current sensor comprises a servo winding (15) in which circulates an induced servocontrol current, and a synchronous servo demodulator (30) for multiplying the servocontrolled current by a demodulation signal of frequency 3.f0. The synchronous servo synchronization demodulator is connected to the excitation module for controlling the excitation voltage so as to cancel a frequency component 3.f0 of the servo-induced current.
    公开号:FR3060757A1
    申请号:FR1662794
    申请日:2016-12-19
    公开日:2018-06-22
    发明作者:Francois Guillot
    申请人:Safran Electronics and Defense SAS；
    IPC主号:
    专利说明:

    ® FRENCH REPUBLIC
    NATIONAL INSTITUTE OF INDUSTRIAL PROPERTY © Publication number: 3,060,757 (to be used only for reproduction orders)
    ©) National registration number: 16 62794
    COURBEVOIE © Int Cl 8 : G 01 R 15/14 (2017.01), G 01 R 33/04
    A1 PATENT APPLICATION
    ®) Date of filing: 19.12.16. ® Applicant (s): SAFRAN ELECTRONICS & (© Priority: DEFENSE Simplified joint-stock company - FR. @ Inventor (s): GUILLOT FRANÇOIS. ©) Date of public availability of the request: 22.06.18 Bulletin 18/25. ©) List of documents cited in the report preliminary research: Refer to end of present booklet (© References to other national documents ® Holder (s): SAFRAN ELECTRONICS & DEFENSE related: Joint stock company. ©) Extension request (s): ® Agent (s): CABINET BOETTCHER.
    CURRENT SENSOR WITH FLOW VALVE.
    FR 3 060 757 - A1 _ Current sensor with flow valve comprising an excitation winding (13), an excitation module (20) intended to generate an excitation voltage (Ve), a measurement winding (14 ) in which a measurement induced current (lim) flows, a synchronous measurement demodulator (22) intended to multiply the measurement induced current by a demodulation signal of frequency 2.f0 to obtain an image voltage of the current to be measured. The excitation voltage (Ve) is obtained from a first voltage of frequency fO and a second voltage of frequency 3.f0, the current sensor with flow valve comprises a servo winding (15) in which flows an induced servo current, and a synchronous servo demodulator (30) intended to multiply the induced servo current by a demodulation signal of frequency 3.f0. The synchronous servo demodulator is connected to the excitation module to slave the excitation voltage so as to cancel a frequency component 3.f0 of the induced servo current.
    z, o A ^
    The invention relates to the field of flow valve current sensors.
    BACKGROUND OF THE INVENTION
    A flow valve current sensor uses the property of a magnetic material forming a magnetic core to saturate from a certain level of magnetic excitation. With reference to FIG. 1, for an increasing magnetic field H, the slope of the transfer function between the magnetic field H and the magnetic induction B decreases greatly from a so-called saturation value of the magnetic core. The saturation value, in FIG. 1, corresponds to the intervals ΔΗ and ΔΒ.
    With reference to FIGS. 2 and 3, in a current flow valve current sensor 1 intended to measure a current Im flowing on a conductor, a rectangular signal generator 2 applies a rectangular excitation voltage Ve across the terminals of a winding excitation 3 wound around a magnetic core 4. The excitation current flowing in the excitation winding 3 is measured by a measurement module 5. A peak detector 6, connected to the measurement module 5, provides two pieces of information: the saturation level and the difference of the peak currents of the excitation current le. The saturation level allows the amplitude of the excitation voltage Ve to be controlled. The difference of the peak currents of the excitation current allows it to estimate the current to be measured Im and to control, via a voltage converter into current 7, the amplitude of a demagnetization current which circulates in a winding of demagnetization 8 and which makes it possible to compensate for the magnetic flux produced in the magnetic core 4 by the current to be measured Im.
    Flow valve current sensors are preferred in a number of applications. This is particularly the case for the measurement of a current flowing in a SSPC (for “Solid State Power Controller”) type breaking device intended for user equipment, or for the measurement of a current flowing in a PEM type energy conversion unit (for “Power Electronic Module”) connected to a phase of a motor.
    Conventional flow valve current sensors suffer from some weaknesses. In particular, peak detection is relatively sensitive to external electromagnetic disturbances, which can therefore degrade the measurement accuracy of the current to be measured. In addition, the peak detection does not give precise information allowing the enslavement on the saturation bend of the magnetic core. This is particularly problematic when the external electromagnetic disturbances are significant, for example in the environment of a switching power converter. It is the same when the current flow valve current sensor 1 is constrained by a difficult thermal environment causing the intrinsic characteristics of the magnetic core to be derived.
    Of course, this problem of precision is all the more important as the frequency range of the current to be measured Im increases (when the current to be measured is an alternating current), or else when the operating temperature range of the current sensor to flow valve increases.
    OBJECT OF THE INVENTION
    The object of the invention is to improve the accuracy of a current sensor with a flow valve.
    SUMMARY OF THE INVENTION
    In order to achieve this goal, a flow valve current sensor is proposed comprising a magnetic core which extends around a conductor on which a current to be measured flows, an excitation winding, a module for excitation connected to the excitation winding and intended to generate an excitation voltage across the excitation winding, a measurement winding in which a measurement induced current flows, a synchronous measurement demodulator connected to the measurement winding and intended for multiply the induced measurement current by a demodulation signal of frequency 2.f0 to obtain an image voltage of the current to be measured. The excitation voltage is obtained from a first frequency voltage fO and a second frequency voltage
    3.f0. The current sensor with flow valve further comprises a servo winding in which a induced servo current flows, and synchronous servo servo connected and intended to multiply the induced servo current by a demodulation signal. frequency 3.f0. The synchronous servo demodulator is connected to the excitation module to slave the excitation voltage so as to cancel a frequency component 3.f0 of the induced servo current.
    The current sensor with flux valve according to the invention allows to precisely control the excitation voltage so that the current sensor with flux valve operates on its operating point a demodulator with the optimal winding, corresponding to the elbow 9 transfer visible in the figure optimal operation corresponds current sensor to flow valve to flow valve is thus external electromagnetic disturbances and therefore more precise.
    of the function of
    1. The point of i a maximum gain of The current sensor less sensitive to
    The invention will be better understood in the light of the following description of a particular, non-limiting embodiment of the invention.
    BRIEF DESCRIPTION OF THE DRAWINGS
    Reference will be made to the appended drawings, among which:
    FIG. 1 represents the curve of a transfer function between a magnetic field and a magnetic induction;
    FIG. 2 represents a flow sensor current sensor according to the prior art;
    FIG. 3 represents the curve of an excitation voltage and the curve of an excitation current which excite a magnetic core of a current sensor with flow valve according to the prior art;
    FIG. 4 represents a flow sensor current sensor according to the invention;
    FIG. 5 represents an excitation module of the flow sensor current sensor according to the invention;
    FIG. 6 represents an example of a synchronous demodulator for measuring the current sensor with a flow valve according to the invention;
    FIG. 7 represents curves of voltages coming from the current sensor with flow valve according to the invention subjected to the field emitted by a conductor traversed by a direct current;
    FIG. 8 represents an excitation voltage used in the flow sensor current sensor according to the invention;
    FIG. 9 represents a square signal and a triangular signal;
    FIG. 10 represents a square signal, a square signal of triple frequency, and the sum of these signals;
    FIG. 11 represents an example of a particular metering circuit of the excitation signal;
    FIG. 12 represents a curve of a voltage at the output of a synchronous demodulator for controlling the current sensor with flow valve according to the invention, as a function of an excitation voltage.
    DETAILED DESCRIPTION OF THE INVENTION With reference to FIG. 4, the flow valve current sensor according to the invention 10 is used here to measure a current to be measured Im which flows on a conductor 11.
    The flow valve current sensor 10 comprises a transformer comprising a magnetic core 12 as well as four coils wound around the magnetic core
    12. The magnetic core 12 extends around the conductor
    11.
    The four windings include an excitation winding 13, a measurement winding 14, a servo winding 15 and a demagnetization winding 16. The measurement winding 14 and the servo winding 15 each consist of a winding double.
    The excitation coil 13 is used to excite the magnetic core 12.
    The flow valve current sensor 10 further comprises a low frequency generator 18, a high frequency generator 19 and an excitation module 20 which is connected to the excitation winding 13.
    The low frequency generator 18 transmits a signal C to the two demodulators 42, 43, 34 and 35. The high frequency generator 19 transmits to the excitation module 20 a signal 1H at the frequency fO (in sin (œOt), with ωΟ = 2ΠΐΟ ), as well as a 3H signal at the frequency 3.f0 (sin (3m0t), with m0 = 2nf0).
    With reference to FIG. 5, the excitation module comprises a plurality of functional blocks, among which a first amplifier block 21 with variable gain, a second amplifier block 22 with variable gain, a summing block 23, a gain block 24.
    The first amplifier block 21 receives the signal 1H at the frequency f0, the second amplifier block 22 receives the signal 3H at the frequency 3.f0, the gain block 24 receives a gain setpoint Cg. The summing block 23 adds the outputs of the first amplifier block 21 and the second amplifier block 22.
    The excitation module 20 thus makes it possible to generate an excitation voltage Ve from a first voltage VI of frequency f0 and from a second voltage V2 of frequency 3, f0.
    The measurement winding 14 is used to measure the current Im. The flow valve current sensor 10 comprises a synchronous measurement demodulator 32, a first low-pass filter 33 and a first unit gain block 34, which are connected in series with the measurement winding 14. The first gain block unit 34 produces a gain selectively equal to 1 or -1. The first unit gain block 34 receives a chopping signal C from the low frequency generator 18. The synchronous measurement demodulator 32 is connected to a first selection block 35. The first selection block 35 receives from the low frequency generator 18 a signal from switching C and the high frequency generator 19 a 2H frequency signal
    2.f0. The first selection block 35 produces a demodulation signal of frequency 2.f0 denoted respectively 2H or 2H according to whether it is in phase or in phase inversion with the signal 2H at frequency 2. f0. The demodulation signal 2H- / 2H is a signal in cos (2œ0t), where ω0 = 2Πί0. The synchronous measurement demodulator 32 multiplies by the demodulation signal 2H- / 2H an induced measurement current lim flowing in the measurement winding 14 and induced by the current to be measured Im. A first integral proportional corrector 37, connected to the first unit gain block 34, produces an image voltage Vi of the current to be measured Im.
    With reference to FIG. 6, the synchronous measurement demodulator 32 includes an analog switch using fast switches 38 of the MOS type. The first low pass filter 33 is a passive filter. The analog switch is clocked by the demodulation signal 2H- / 2H in phase or in phase inversion. The voltage Vs at the output of the first low-pass filter 33 is an image voltage of the harmonic component of order 2 of the excitation voltage Ve.
    With reference to FIG. 7, it is noted that the saturation of the magnetic core 12 causes an asymmetry of the induced measurement current Iim, said induced measurement current Iim being constituted by the sum of a frequency component fO in sin (mOt), corresponding to the fundamental, and a frequency component 2.f0 in cos (2œ0t), corresponding to the harmonic component of order 2. The average component of the demodulated signal Sd is non-zero and positive. By taking the opposite of saturation, the average component of the demodulated signal Sd becomes negative.
    The servo winding 15, in which an induced servo current lia flows, is used to control the excitation voltage Ve current at the flow valve 10 comprises synchronous servo 40, a second low-pass filter 41 and a second block unit gain 42, which are connected in series with the servo winding 15. The second unit gain block 42 produces a gain selectively equal to 1 or to -1. The second unit gain block 42 receives a continuous signal C from the low frequency generator 18. The synchronous demodulator
    The sensor of a servo demodulator 40 is connected to a second selection block 43. The second selection block 43 receives from the low frequency generator 18 a chopping signal C and from the high frequency generator a signal 3H of frequency 3, f0. The second selection block 43 produces a demodulation signal 3H- / 3H of frequency 3, f0 in phase or in phase inversion. The demodulation signal 3H- / 3H is a sin signal (3o0t), where ω0 = 2Πί0. The synchronous servo demodulator 40 multiplies by the demodulation signal 3H- / 3H the induced servo current 11a. A second integral proportional corrector 44 is connected between the second unit gain block 42 and the excitation module 20. The excitation voltage Ve is thus controlled so as to cancel the frequency component 3.f0 of the induced servo current lia.
    The synchronous servo demodulator 40 is similar to the synchronous measurement demodulator 32, visible in FIG. 6, except that the analog switch is clocked by the demodulation signal 3H / 3H in phase or in phase inversion.
    The demagnetization winding 16, for its part, is connected to the output of the first integral proportional corrector 37 via a voltage to current converter 45. A demagnetization current Id flows in the demagnetization winding 16 to demagnetize the magnetic core 12.
    The image voltage Vi of the current to be measured Im, at the output of the first integral proportional corrector 37, is applied at the input of the voltage to current converter 45. The voltage to current converter 45 produces the demagnetization current Id from the image voltage Vi of the current to be measured Im. The current at the output of the first unit gain block 34 forms a current setpoint applied at the input of the first proportional corrector 37. The demagnetization current Id is thus controlled from the image voltage Vi of the current to be measured Im so as to compensate for the magnetic flux produced by the current to be measured Im.
    The characteristics of the excitation voltage Ve will now be described in more detail.
    With reference to FIG. 8, the amplitude of the first voltage VI and the amplitude of the second voltage V2 are adjusted to obtain an excitation voltage Ve whose frequency component 3.f0 (or harmonic component of order 3 ) is in phase with the frequency component fO (or fundamental).
    The harmonic component of order 3 of the induced servo current lia flowing in the servo winding 15, obtained after synchronous demodulation via the synchronous servo demodulator 40, is positive. In the event of saturation of the magnetic core 12, the harmonic component of order 3 is attenuated more strongly than the fundamental and the harmonic component of order 3 after synchronous demodulation becomes negative, because the harmonic of order 3 goes into phase opposition with the fundamental.
    Thus, when the excitation voltage Ve is such that the magnetic core 12 approaches saturation, the ratio of the amplitude of the harmonic component of order 1 and the amplitude of the harmonic component of order 3 of the induced servo current lia evolves until the harmonic component of order 3 is canceled, then until phase inversion of the harmonic component of order 3. The operating point corresponding to the cancellation of the harmonic component d order 3 of the induced servo current 11a is therefore an optimal operating point of the flow sensor current sensor 10. This optimal operating point corresponds to the elbow 9 of the transfer function curve of FIG. 1.
    ίο
    The control of the excitation voltage Ve therefore consists in controlling the excitation voltage Ve, before this is applied to the terminals of the excitation winding 13, in order to cancel the harmonic component of order 3 of the induced current. servo lia. The flow valve current sensor 10 thus operates continuously at the optimum operating point. In this way, a maximum gain is obtained for the asymmetries introduced by the current to be measured Im and detectable on the induced measurement current Iim. It is noted that this servo-control by synchronous demodulation of the harmonic component of order 3 is not very sensitive to external electromagnetic disturbances, because all the signals of frequency different from the frequency 3.f0 generate intermodulation products whose components are filtered by the first low-pass filter 33 connected to the output of the synchronous measurement demodulator
    32. It should also be noted that this enslavement does not need to be very rapid, since the variations coming from external parameters (temperature, aging) are relatively slow.
    As can be seen in FIG. 7, the first voltage VI and the second voltage V2 are here both rectangular voltages. Rectangular voltages are indeed simple to generate, and have important odd harmonic components.
    The advantage of using such an excitation voltage Ve constituted by such a first voltage VI and such a second voltage V2 follows from the following.
    With reference to FIG. 9, the spectral decomposition of a square signal 50 of amplitude E and of period T is:
    X (t) = 4. E / Π. [sin (œt) +1/3. sin (3cùt) +1/5. sin (5œt) + ...], with ω = 2Π / Τ.
    The spectral decomposition of a triangular signal of amplitude E and of period T is:
    X (t) = 8. Ε / ΓΊ 2 . [sin (œt) -1/3 2 . s in (3œt) + 1/5 2 . s in (5œt), with ω = 2Π / Τ.
    The triangular signal 51 therefore has a negative order 3 harmonic component.
    In reference at the figure 10, the addition of a first voltage VI of form rectangular and of a second voltage V2 of form rectangular, allows,
    when the amplitude of the first voltage VI and the second voltage V2 are correctly adjusted, to obtain an excitation voltage Ve of generally triangular shape whose harmonic component of order 3 is negative.
    The saturation phenomenon of the magnetic core 12 will bring the waveform of the induced servo current 11a closer to the waveform of a square signal. Approaching saturation, the amplitude of the harmonic component of order 3 of the induced servo current lia will therefore tend towards zero, then become negative, in accordance with the decomposition of a square signal. An excitation voltage control Ve is thus defined by servo-control on the point of cancellation of the harmonic component of order 3 of the induced servo-current ia.
    We can find by calculation this particular point of regulation.
    The first voltage VI presents the following spectral decomposition, into sinusoidal functions:
    Xl (t) = 4 .Ε1 / Π. [sin (mOt) +1/3. sin (3to0t) +1/5. sin (5œ0t) + ...].
    The second voltage V2 has the following spectral decomposition, into sinusoidal functions:
    X2 (t) = 4. Ε2 / Π. [sin (3m0t) + l / 3.sin (9M0t) + l / 5.sin (15m0t) + ...].
    The harmonic component of order 3 of the sum between, on the one hand, the spectral decomposition of the first voltage VI and, on the other hand, the second spectral decomposition of the second voltage V2 is equal to:
    4 / Π. (El / 3.sin (3m0t) + E2.sin (3m0t).
    The harmonic component of order 3 is therefore zero for E1 = -3.E2.
    The control of the excitation voltage Ve consists in controlling the amplitude of the second voltage V2. We therefore play on the amplitude of the second voltage V2 to control the excitation voltage Ve so as to cancel the frequency component 3.f0 of the induced servo current lia.
    The excitation voltage control Ve sought must therefore, before saturation of the magnetic core 12, include a level of relative excitation by the harmonic component of order 3 giving a slightly negative result after demodulation by the synchronous servo demodulator 40 for power, during saturation, go through 0 then become negative. It is this particular point that must be adjusted in order to find the best gain compromise of the transfer function, which corresponds to the optimal operating point and at the elbow 9 of the transfer function visible in FIG. 1.
    We note the signal 2H of frequency 2. f0 and the signal 3H of frequency 3.f0 are periodically reversed in phase, here at a frequency of 10kHz. The shifts in phase opposition are averaged by the first integral proportional corrector 37 and by the second integral proportional corrector 44, and therefore canceled. This 10kHz phase inversion function compensates for imbalances in the measurement and servo channels, which result from imperfections in the analog components used. This improves the precision of the adjustment of the flow valve sensor 10 to the optimum operating point, and therefore the overall precision of the flow valve sensor 10 itself.
    With reference to FIG. 11, a first amplifier 53 mounted in buffer, two first output resistors 54 of 15Ω each, a first adjustment resistor 55, a second amplifier 56 mounted in buffer is used to adjust the excitation voltage Ve. two second output resistors 57 of 15Ω each and a second adjustment resistor 58. An excitation voltage such as El = 2.78E2 is thus applied to a load 59. The value 2.78 is less than 3, and therefore the level of the harmonic component of order 3 of the excitation voltage Ve is higher than that of a square signal, which corresponds to a negative demodulated signal.
    Referring to Figure 12, the harmonic component of the voltage 60 at the output of the synchronous servo demodulator 40 is canceled for an excitation voltage close to 3V and becomes positive beyond. The zero crossing therefore corresponds to the optimum operating point of the flow sensor current sensor 10. By controlling the induced servo current lia at this zero crossing point, the transfer function of the flow sensor current sensor according to the invention 10 remains in the bend 9 in FIG. 1.
    The flow valve current sensor 10 has a number of advantages over existing flow valve current sensors.
    The improvement of the regulation of the operating point thanks to demodulation by the synchronous servo demodulator 40 makes it possible to obtain better immunity to noise.
    In addition, the use of synchronous demodulators makes it possible to operate at high frequency, which allows a significant bandwidth of the current to be measured Im while retaining very good immunity to external electromagnetic disturbances.
    As the measurement is always made at the optimal operating point corresponding to the saturation bend 9, the sensitivity of the flow sensor current sensor 10 is constant in the temperature range. The accuracy of the flow valve current sensor 10 is therefore good in a large temperature range.
    The flow valve current sensor 10 is insensitive to drifts in the manufacture of certain characteristics of the magnetic core 12. In particular, the magnetic permeability characteristics of conventional magnetic cores, which are not intended to be used in their saturation zone, are very disparate. The precise control of the operating point makes it possible to correct these dispersions. Standard magnetic cores can therefore be used, which reduces the industrial constraints of manufacturing the magnetic core, and therefore the cost of the flow sensor current sensor 10. It is thus possible, for example, to use a ferrite magnetic core conventionally used in power converters and for certain radio functions.
    Note also that the flow valve current sensor 10 has an architecture which can be transposed to digital solutions to improve the reproducibility and therefore the manufacture of the flow valve current sensor 10. Thus, the excitation voltage Ve can be produced by a fast analog-to-digital converter. Likewise, the synchronous demodulators 32 for measurement and servo control 40 can be implemented on a digital component (for example, on an FPGA). Demagnetization can also be done via a digital analog converter.
    Note that it would be possible to use not just one but two magnetic cores. The second magnetic core would receive the same excitation as the measurement circuit, but in phase opposition, to cancel the flux directly at the level of the conductor on which the current to be measured flows.
    Of course, the invention is not limited to the embodiment described but encompasses any variant coming within the scope of the invention as defined by the claims.
    权利要求:
    Claims (7)
    [1" id="c-fr-0001]
    1.
    a conductive core (Im), an excitation (20) intended to generate
    Flow sensor current sensor comprising magnetic (12) which extends around one (11) on which a current to be measured excitation winding (13) flows, a module connected to the excitation winding and a voltage d excitation terminals of the excitation winding, a measurement winding (14) in which a measurement induced current (Iim) flows, a synchronous measurement demodulator (32) connected to the measurement winding and intended to multiply the measurement induced current by a demodulation signal of frequency 2, f0 to obtain an image voltage of the current to be measured, characterized in that the excitation voltage (Ve) is obtained from a first voltage (Vl) of frequency fO and d a second voltage (V2) of frequency 3.f0, in that the current sensor with flow valve further comprises a servo winding (15) in which a induced servo current flows, and a synchronous demodulator of servo (40) connected servo winding and desti born to multiply induced servo current by a demodulation signal of frequency 3.f0, and in that synchronous servo demodulator is connected to the excitation module to slave the excitation voltage so as to cancel a frequency component 3 .f0 of the induced servo current.
    [2" id="c-fr-0002]
    2. A flow valve current sensor according to claim 1, in which the first voltage (VI) and the second voltage (V2) are rectangular voltages.
    [3" id="c-fr-0003]
    3. Flow valve current sensor according to claim 1, in which the excitation voltage (Ve) has a generally triangular shape.
    (Ve) aux au le de
    [4" id="c-fr-0004]
    4. A flow valve current sensor according to claim 1, in which the control of the excitation voltage consists in controlling the amplitude of the second voltage (V2).
    [5" id="c-fr-0005]
    5. A flow valve current sensor according to claim 1, in which the frequency demodulation signal 2. f 0 is a signal in Cos2cù0t, where ωΟ = 2ΠίΟ.
    [6" id="c-fr-0006]
    6. Flow valve current sensor according to claim 1, further comprising a winding of
    [7" id="c-fr-0007]
    10 demagnetization (16) in which a demagnetization current (Id) flows which is controlled from the image voltage of the current to be measured to compensate for a magnetic flux produced by the current to be measured (Im).
    > 4 / -Ο s σ>
    where
    3 / £ <_ £>
    (Τ'-.
    "Ο
    Ά
    C c-n r
    O- 25
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    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    US3435337A|1964-12-11|1969-03-25|Trw Inc|Superconductive fluxgate magnetometer|
    EP0137347A1|1983-09-15|1985-04-17|Danfysik A/S|A detector circuit for current measurements|
    WO1991013366A1|1990-02-28|1991-09-05|Nippon Kokan Kk|Method and apparatus for magnetic detection|
    EP1746430A1|2005-07-22|2007-01-24|Liaisons Electroniques-Mecaniques Lem S.A.|Orthogonal fluxgate magnetic field sensor|
    US20080252289A1|2005-10-07|2008-10-16|Billanco|Current and Magnetic Field Sensors, Control Method and Magnetic Core For Said Sensors|
    FR2942880A1|2009-03-04|2010-09-10|Commissariat Energie Atomique|Current sensor i.e. single-phase current sensor, has coils electrically connected in series between terminals of electrical signal processing unit such that electrical signal is null when coils are placed in same magnetic field|
    WO2014047644A2|2012-09-24|2014-03-27|Shane Clamme|Measuring dc current with a current transformer|
    WO2016016038A1|2014-07-30|2016-02-04|Lem Intellectual Property Sa|Current transducer with fluxgate detector|WO2020002184A1|2018-06-27|2020-01-02|Safran Electronics & Defense|Current sensor with flux gate|JPH11281678A|1998-03-30|1999-10-15|Shimadzu Corp|Current sensor|
    DE102007032300A1|2007-07-11|2009-01-22|Siemens Ag|Current sensor for direct current or alternating current measurements, comprises two flux gate sensors, where every flux gate sensor has magnetic core, and current carrying conductor is assigned two conductive sections|
    EP2587268A1|2011-10-26|2013-05-01|LEM Intellectual Property SA|Electrical current transducer|
    CN202330528U|2011-11-28|2012-07-11|河北工业大学|Current sensor with double-shaft fluxgate|
    EP2682762A1|2012-07-06|2014-01-08|Senis AG|Current transducer for measuring an electrical current, magnetic transducer and current leakage detection system and method|
    RU2555200C2|2013-08-06|2015-07-10|Феликс Матвеевич Медников|Method of temperature compensation of inductive position sensor and device for its implementation|
    CA2868663C|2013-10-21|2016-11-08|Tomasz Barczyk|Methods and systems relating to ac current measurements|
    CN104374982A|2014-07-25|2015-02-25|中国计量科学研究院|Non-contact direct current measuring circuit and method|
    US9523719B2|2014-10-10|2016-12-20|Bose Corporation|Current sensor|DE102018130690B3|2018-12-03|2020-03-26|Bender Gmbh & Co. Kg|Magnetic field measuring device and method for detecting a localization current in a branched AC power supply system|
    US11047928B2|2019-07-15|2021-06-29|Allegro Microsystems, Llc|Methods and apparatus for frequency effect compensation in magnetic field current sensors|
    法律状态:
    2017-11-20| PLFP| Fee payment|Year of fee payment: 2 |
    2018-06-22| PLSC| Publication of the preliminary search report|Effective date: 20180622 |
    2019-11-20| PLFP| Fee payment|Year of fee payment: 4 |
    2020-11-20| PLFP| Fee payment|Year of fee payment: 5 |
    2021-11-18| PLFP| Fee payment|Year of fee payment: 6 |
    优先权:
    申请号 | 申请日 | 专利标题
    FR1662794|2016-12-19|
    FR1662794A|FR3060757B1|2016-12-19|2016-12-19|FLOW VALVE CURRENT SENSOR|FR1662794A| FR3060757B1|2016-12-19|2016-12-19|FLOW VALVE CURRENT SENSOR|
    PCT/EP2017/083671| WO2018115032A1|2016-12-19|2017-12-19|Current sensor with fluxgate|
    EP17821617.2A| EP3555642A1|2016-12-19|2017-12-19|Current sensor with fluxgate|
    RU2019122657A| RU2718758C1|2016-12-19|2017-12-19|Inductive current sensor|
    US16/470,480| US10884028B2|2016-12-19|2017-12-19|Current sensor with fluxgate|
    CN201780078327.2A| CN110088636B|2016-12-19|2017-12-19|Current sensor with fluxgate|
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