• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    The invention relates to a device for supplying a plurality of loads (14) from an electrical energy supply network (25), comprising a plurality of converters (16) supplied with electrical energy by the network ( 25) for converting and supplying electrical energy to at least one load (14). The device includes a controller (17) for associating multiple converters (16) in parallel to supply at least one load (14) in response to a power requirement of the at least one load (14). Each of the converters (16) includes distributed means (33) for limiting recirculation currents generated by the parallel association of a plurality of converters (16).
    公开号:FR3015145A1
    申请号:FR1302974
    申请日:2013-12-18
    公开日:2015-06-19
    发明作者:Frederic Lacaux；Christophe Bruzy；Jacques Casutt
    申请人:Thales SA；
    IPC主号:
    专利说明:

    [0001] The invention relates to a modular and reconfigurable power supply device for a plurality of loads from an electrical energy supply network. More specifically, it relates to an aircraft power supply device capable of limiting the recirculation currents generated during the paralleling of converters dedicated to the supply of the same load. Large aircraft have more and more embedded electrical equipment. These equipments are of a very varied nature and their energy consumption is very variable over time. For example, aircraft flight controls, air conditioning and internal lighting systems are in almost continuous operation, while engine starting systems, electric braking systems, or redundant safety steering controls, are only used for short periods of time during a mission. Generally, the aircraft has a three-phase electrical power supply network for supplying all the electrical equipment called charges thereafter. The different charges may require different energy inputs in voltage and in kind of current, alternating or continuous. Moreover, the loads can be more or less tolerant to the disturbances of the electrical network which supplies them. In most current aircraft power supply systems, each load is associated with its own converter and its dedicated filtering network. Attempts have been made to implement a more modular power supply structure for dynamically allocating one or more converters to electrical loads according to the power requirements thereof. In particular, it was noted that the patent application published under the reference FR0603002 describes the principle of a modular power supply device. Figure 1 of the present application illustrates the principle of such a modular electrical architecture. A supply network 3015 14 5 of electrical energy 10 comprises for example several electric generators 11 on board the aircraft. The network may also include batteries for storing electrical energy. It may also include means of connection to a ground power supply network, allowing the power supply of the aircraft parked on a runway. The electrical energy supply network 10 comprises conversion means 12 and filtering 13 for implementing the electrical signal generated by the generators 11 and transmitted to the onboard network. This power supply network 10 allows the supply of a plurality of loads 14. It may be air conditioning systems ECS, for the acronym Environmental Control Systems, MES motor starting systems, for the English acronym Main Engine Start, or EMP hydraulic pumps, for the acronym Electro Mechanical Pump implemented for example for the control of flight control.
    [0002] Between the power supply network 10 and the plurality of loads 14, a modular power supply device 15 is intended to allocate in real time to each load one or more converters 16 according to the power requirements of the load . It is envisaged to combine in parallel several converters 16 making it possible to supply the level of power required for a load 14. The paralleling of converters 16, by a real-time allocation controlled by a control member, to the plurality of loads 14, makes it possible to optimize the on-board conversion power and therefore to limit the weight and the cost of the conversion elements. To reduce the electrical noise and to be able to meet EMI requirements, for the acronym Electro Magnetic Interference, it is used techniques of filtering and interlacing associated converters in parallel. The interleaving of the signals of two converters in parallel is illustrated in FIG. 2. The filtering integrated in the converters is optimized by the interleaving in real time both at the input 20 of the converters 16 and at the supply network side. electrical energy 10, and the output 21 of the converters 16, the electric charge side 14. The switching frequency and type of duty cycle opening control, or PWM, can also be adapted in real time to optimize the size and weight of the filters.
    [0003] The implementation of a modular and reconfigurable power supply device is therefore based on the ability to parallelize and interleave several converters dynamically. The paralleling and / or interleaving is, however, hampered by difficulties related in particular to the generation of recirculation currents between the converters. These recirculation currents significantly increase the total current seen by the active components of the converters. To support these high currents, a large oversizing of the components becomes necessary. The adaptation of the converters to the recirculation currents by suitable sizing of the active components (thermally, electrically, EMI) is in practice unrealistic; the weight, the volume and the cost of such a converter being unsuitable. In order to overcome the difficulties posed by the generation of recirculation currents, one solution envisaged is to implement between the converters connected in parallel an interphase inductance, also called an interphase choke. Figure 3 illustrates the principle of using an interphase choke for the parallel combination of two converters. In this example, two converters 16 are supplied in parallel by the same electrical source 25. The outputs 21 of the two converters 16 are connected to an interphase choke 26. The interphase choke 26 assembles the signals of the converters' outputs 21 The parallel association of two converters 16 generates recirculation currents shown and referenced iZ in FIG. 3. The interphase choke 26 is used to generate a zero-sequence impedance, also called an impedance. Zero sequence, important to reduce the recirculation currents, in particular the high frequency recirculation currents. This solution consists of connecting one to one of the three phases of the two converters by means of an interphase choke. This solution effectively limits the recirculation currents, but its major drawback is the addition of an element between the converters. For a complex power supply architecture, employing a large number of sources and electrical loads, it is necessary to add as many interphase chokes as envisaged combinations of converters. In addition, the filtering represented by the module 28 in FIG. 3, must be performed at the output of the interphase choke. In other words, the addition of an interphase choke between the converters involves implementing a centralized filtering system, and not distributed within each of the converters. The use of an interphase self and thus a centralized filtering for each combination of converters envisaged limits the modularity of the architecture. It is only possible to switch statically between predefined configurations imposed by the structure of the interphase chokes. The number and mass of interphase chokes can become significant and in practice limits modularity and reconfigurability to a small number of configurations. In summary, the implementation of a modular power supply architecture capable of distributing conversion capacity according to the instantaneous electrical power requirements of the different electrical loads has many benefits. However, it has been found that the parallel association of converters is in practice difficult because of the recirculation currents generated between the converters. This problem remains to be solved because the immediate solution of having an interphase choke between associated converters in parallel does not allow sufficient modularity. The object of the invention is to provide a modular and reconfigurable power conversion device that overcomes these difficulties. To this end, the subject of the invention is a device for supplying a plurality of loads from an electrical energy supply network, comprising several converters, supplied with electrical energy by the network, ensuring the conversion. and supplying electrical energy to at least one load. The device includes a controller configured to associate multiple converters in parallel to supply at least one load, in response to a power requirement of the at least one load. Each of the converters comprises distributed means for limiting recirculation currents generated by the parallel association of several converters. Advantageously, the distributed means of each of the converters are configured to generate a high-sequence zero impedance opposing the creation of recirculation current between the associated converters in parallel.
    [0004] Advantageously, each of the converters delivers electrical energy to the at least one charge in N1 phases. The distributed means of each of the converters comprises a homopolar component blocking transformer, also called a zero sequence transformer coupling the N1 phases, configured to generate a high zero sequence impedance allowing to oppose, for "each phase, the creation of high frequency recirculation current between the converters Advantageously, each of the converters delivers electrical energy to the at least one load in N1 phases, and the distributed means of each of the converters comprise for each of the N1 phases an inductance of differential mode, configured to generate a high zero sequence impedance to oppose, for each phase, the creation of high frequency recirculation current between the converters.
    [0005] Advantageously, each of the converters comprises filtering means associated with the transformer of each of the N1 phases. Advantageously, each of the converters delivers three-phase AC electrical energy to the at least one load. Advantageously, each of the converters is supplied with electrical energy by the supply network in N2 phases, and the distributed means of each of the converters comprise a transformer coupling the N2 phases, configured to generate a zero sequence impedance to oppose, for each phase, the creation of high frequency recirculation current between the converters. Advantageously, each of the converters comprises filtering means associated with the transformer coupling the N2 phases. Advantageously, each of the converters is supplied with electrical energy by a continuous electrical network. Advantageously, the distributed means of each of the converters comprise a zero-sequence current regulator, also referred to as a zero-sequence regulator configured to control the common-mode voltage of each of the converters so as to cancel the common-mode current of the N1-phases, allowing to oppose the creation of low frequency recirculation current between the converters.
    [0006] Advantageously, the distributed means of each of the converters are configured to cancel common mode voltage differences between the associated converters in parallel. Advantageously, the converters deliver energy to the at least one load in N1 phases, and the distributed means of each of the converters comprise a conversion element complementary to the conversion means into N1 phases and a filtering element, allowing a active mode common voltage filtering in each of the converters (16). The invention will be better understood and other advantages will become apparent upon reading the detailed description of the embodiments given by way of example in the following figures. FIG. 1, already presented, represents an example of a modular and reconfigurable power supply architecture envisaged in the state of the art, FIG. 2, already presented, illustrates the principle of interleaving between two associated converters. FIG. 3 illustrates the principle of the use of an interphase choke for the parallel association of two converters. FIG. 4 illustrates the principle of the generation of recirculation currents linked to the In parallel, FIGS. 5a and 5b show two embodiments of a power supply device comprising means for limiting high frequency recirculation currents, FIG. 6 represents a third embodiment of an embodiment of the invention. power supply device comprising means for limiting high frequency recirculation currents, FIG. a fourth embodiment of a power supply device comprising complementary means for limiting low-frequency recirculation cameras, FIG. 8 shows a fifth embodiment of a power supply device comprising means for canceling out low-frequency recirculation cameras. common mode voltage differences, FIG. 9 shows the parallel association of N converters by means of a power supply device according to the first embodiment, FIG. 10 represents the functional architecture of FIG. a control member operable in the feeder, Fig. 11 shows an embodiment of a low level control module of the controller, Figs. 12a and 12b show an embodiment of an intermediate control module of the control member, FIG. 13 represents an embodiment of a system control module of the control member. For the sake of clarity, the same elements will bear the same references in the different figures. Figures 4 to 8 describe several embodiments of the invention in the most common case of a power supply of the converters 16 by a continuous power supply network. The charges 14 are powered by three-phase alternating voltages. In other words, for each of the converters 16, the input 20 comprises two polarities and the output 21 comprises three phases. This choice corresponds to the most widespread case in the aeronautical field. This choice is not, however, limiting of the present invention. It is also envisaged to implement the invention in different configurations, in nature of current / voltage and in phase number, both in input and in output of the converters. In this sense, FIGS. 9 and 10 describe the case of parallel associated converters for N1 phase charge feed from a N2 phase electrical power supply network. FIG. 4 illustrates the principle of the generation of recirculation currents linked to the association of converters in parallel. The paralleling and / or interleaving of several converters is capable of generating two types of recirculation currents: high frequency recirculation currents, generated by the interaction of the breakdowns of the different converters, and recirculation currents low frequencies, due to differences in the control parameters of the different converters. This phenomenon can be modeled by means of a so-called switch function modeling, or more generally by the "switching functions" representation represented in FIG. 4. In this case where two converters are associated in parallel, the modeling shows that the recirculation current is a common mode current, where in each converter, the sum of the phase currents, ia-Fib-Fic, is not zero but equal to a current flowing between the two converters. The current is generated due to the common mode voltage differences between the two converters at each switching period of the converter. To limit the recirculation currents, a first theoretical approach is to create a strong zero sequence impedance between the converters. This high impedance makes it possible to limit the current time evolution di / dt resulting from the common mode voltage differences of the converters. This approach can for example be implemented by adding an interphase choke between converters as previously described. The implementation of an interphase choke between each phase of the converters makes it possible to force the pairs of phase currents (ia, (ib, ib ') and (ic, ic') to values close to zero. is to create a strong zero sequence impedance which opposes the creation of a current io between converters, but we have had the opportunity to clarify the drawbacks in terms of modularity of this solution with an external interphase coil 25 A second theoretical approach consists in canceling the differences in common mode voltages between the converters in parallel As will be described in the following figures, the device according to the invention makes it possible to limit the currents of circulation by means of of the first and / or second theoretical approach, while avoiding the limitations of the existing solutions Figure 5a shows a first embodiment of an electrical power supply device. comprising means for limiting high frequency recirculation currents. In this example, two converters, supplied with electrical energy by the same continuous network 25, are assigned by a control member 17 to a load 14. The two converters 16 convert and feed the load 14 into voltage. three-phase alternative. Each converter 16 comprises, between an input 20 and an output 21, means 30 for filtering the energy supplied by the network 25, DC / AC conversion means 31, and filtering means 32 for the alternative signals generated by the conversion means 31. The filtering means 30 and 32 and the conversion means 31 are conventional components well known to those skilled in the art. Their operation is not described in detail here. Each of the converters 16 also includes distributed means 33a configured to generate a high zero sequence impedance opposing the creation of recirculation current between the associated converters in parallel. In this example, the distributed means 33a comprise a zero sequence transformer 34a connecting the conversion means 31 to the filtering means 32. In each converter, and independently of the other converters, the zero sequence transformer 34a couples the three phases of the converter. by forcing the sum ia + ib + ic = i0 of each converter to values close to zero. At the system level, this corresponds to generating a high zero sequence impedance, making it possible to oppose the creation of high frequency recirculation current between the converters. In other words, this first embodiment is based on the first theoretical approach for reducing the recirculation currents described in the context of FIG. 4. The zero sequence transformer 34a generates a zero sequence impedance by coupling for each converter, each of the phases through the magnetic body. The impedance generated is opposed to the creation of a recirculation mode current by the common mode voltage difference between the converters. These transformers 30 are sized similarly to a common mode filter choke. Simple and controlled technological solutions, such as magnetic core cores or E nanocrystalline materials can be implemented to obtain high impedance values to limit the recirculation currents to relatively low values. FIG. 5b shows a second embodiment of a power supply device comprising means for limiting high frequency recirculation currents. As for the previous embodiment, two converters 16, supplied with electrical energy by the same continuous network 25, are assigned by a control member 17 to a load 14. The two converters 16 provide the conversion and the power supply. of the load 14 in three-phase AC voltage. Each converter 16 comprises, between an input 20 and an output 21, means 30 for filtering the energy supplied by the network 25, DC / AC conversion means 31, and filtering means 32 for the alternative signals generated by The converter means 31. Each of the converters also includes distributed means 33b configured to generate a high zero sequence impedance opposing the recirculation current creation between the associated converters in parallel. In this example, the distributed means 33b comprise for each of the phases a differential mode inductance, or in other words a three-phase differential inductance 34b connecting the conversion means 31 to the filtering means 32. The differential mode inductances are perceived by the component 20 differential and the common mode component of the current. Depending on their value, the differential mode inductors in each converter reduce the sum ia + ib + ic = 10 of each converter to values close to zero. At the system level, they contribute to generating a high zero sequence impedance, making it possible to oppose the creation of high frequency recirculation current between the converters. Thus, this second embodiment also relies on the first theoretical approach of reducing the recirculation currents described in the context of FIG. 4. The differential mode inductors generate a zero sequence impedance. These inductances are sized similarly to a differential mode filter choke. Their sizing can be optimized at the system level. A high differential mode inductance value in each module reduces the common mode current to a low value. But a high differential mode inductance value is penalizing in terms of weight and volume, despite the new magnetic materials. Conversely, a lower value of differential mode inductance increases the value of the recirculation current and thus the ripple and the peak currents in the phases of the conversion means. It is also known that a high current in the switches of the conversion means is detrimental to their operation. Thus, the optimization of the differential mode inductance value results from a compromise between the value of the peak currents per phase, the recirculation currents, and the definition of the switches. Typically, an optimized differential mode inductance value makes it possible to obtain a compatible ripple of the switch definition, minimizing the switching losses by performing smooth switching, without loss of ignition switching at the switches, and without switching loss for blocking diodes. It is interesting to note that in order to comply with the EMI specifications, it is necessary to implement in the converters 16 a differential mode filtering. Differential mode filtering is equivalent to differential mode chokes. An additional optimization is therefore the integration into each of the converters of the differential mode chokes to limit the recirculation current with the differential mode chokes needed to comply with the EMI specifications. This enables the means to be coupled to limit the recirculation currents and differential mode inductances necessary for the EMI requirements by means of a single magnetic component. In other words, appropriate dimensioning of the differential mode inductors makes it possible to integrate the function of the recirculation current limiting means advantageously making it possible to limit the weight of the overall filtering, without involving the implementation of additional components. FIG. 6 represents a second embodiment of a power supply device according to the invention. As before, two converters 16 fed by the continuous network 25 are assigned by a control member (not shown in this figure) to a load 14. Each converter 16 comprises, between an input 20 and an output 21, means for filtering the energy supplied by the network 25, conversion means 31, and filtering means 32 of the alternating signals 35 generated by the conversion means 31.
    [0007] Each of the converters 16 also includes distributed means 43 configured to generate a high zero sequence impedance opposing the creation of recirculation current between the associated converters in parallel. In this example, the distributed means 43 are arranged at the input 20 of the converters 16 and comprise, for each polarity of the continuous network 25, a transformer 44 connecting the input 20 to the conversion means 31. In other words, this second mode of embodiment implements a zero sequence blocking mode transformer in each converter. Each transformer creates a zero sequence impedance by coupling the two input polarities of each converter through the magnetic body of the transformer. As before, the impedance generated opposes the creation of a recirculation mode current by the common mode voltage difference between the converters. The technological solutions already mentioned, such as magnetic cores torus or E, nanocrystalline type materials, can advantageously be implemented. It is interesting to note that to meet the EMI specifications the converter system needs to implement common mode filtering. Typically, this common mode filtering corresponds to a common mode choke coupling the three output phases of the converters. An additional optimization is therefore the integration into each of the modules of the zero sequence blocking transformers with the common mode inductance necessary for the common mode switching noise filtering. This allows the implementation of the zero sequence blocking transformer and the common mode inductor into a single magnetic element. The proper sizing of the zero sequence blocking transformers therefore makes it possible to integrate the common mode filtering function thus minimizing the weight of the overall filtering. The integration into each of the modules of these recirculation current blocking devices and common mode filtering makes it possible not to add additional element for the parallelization of the modules. FIG. 7 shows a fourth embodiment of a power supply device comprising complementary means for limiting low frequency recirculation currents. The first three embodiments described respectively in Figures 5a, 5b and 6 implement means distributed in each of the converters capable of limiting high frequency recirculation currents. The fourth embodiment described in FIG. 7 comprises distributed means similar to the first embodiment, comprising a zero sequence transformer 34 for limiting the high frequency recirculation currents. The fourth embodiment aims to also limit the recirculation currents low frequencies. For this purpose, it associates with the zero sequence blocking transformers limiting the high frequency recirculation currents, a zero sequence regulator for limiting the low frequency recirculation currents. The zero sequence controller can be associated with transformers implemented in the input filters or the output filters. In FIG. 7, each converter 16 comprises means 30 for filtering the energy supplied by the continuous network 25, conversion means 31, and means 32 for filtering the alternating signals generated by the conversion means 31. Each converter also includes distributed means 50 configured to generate a high zero sequence impedance opposing creation of recirculation current between the associated converters in parallel. The distributed means 50 comprise on the one hand a zero sequence transformer connecting the conversion means 31 to the filtering means 32, and on the other hand a zero sequence regulator 51. The zero sequence regulator 51 comprises means for measuring the phase currents ia, ib and ic at the output of the transformers 34, calculating the common mode current ia + ib + ic, and driving the conversion means 31 with a zero common mode current as regulation setpoint. In other words, the regulator 51 makes it possible to reduce the low frequency recirculation currents by controlling the low frequency component of the recirculation current to zero by controlling the common mode voltage by the PWM setpoints of the conversion elements 31. A possibility of a control variable for the common mode voltage is the zero vector distribution of the PWM setpoints between the vector (1,1,1) and the vector (0,0,0). The time of the vector (1,1,1) may be equal to the time of the vector (0,0,0). For a given length of the zero vector, the zero sequence controller can act on the distribution between the vector (1, 1, 1) and the vector (0,0,0) and enslave the common mode voltage at the output of the converter for check the low frequency recirculation current at zero. Each converter thus independently controls its recirculation current, allowing the supply device to cancel all of the recirculation currents without using a common corrector. The principle of this zero sequence regulator distributed in each converter makes it possible to cancel the low frequency recirculation currents. This regulator can be implemented in different ways depending on the applications considered and the topologies of the converters. FIG. 8 represents a fifth embodiment of a power supply device according to the invention. Unlike the previous three, this fifth embodiment is based on the second theoretical approach of reducing the recirculation currents described in the context of FIG. 4. This embodiment is based on the cancellation of the common mode voltage. each of the converters; or in other words on means for active filtering of the common mode voltage. For this, each converter comprises an additional cutting arm. As in the previous figures, each converter 16 comprises means 30 for filtering the energy supplied by the continuous network 25, conversion means 31, and filtering means 32 for three-phase AC signals generated by the conversion means 31. Each converter further comprises distributed means 60 for limiting recirculation currents generated by the parallel association of several converters. The distributed means 60 comprise an additional conversion element 61 integrated in the conversion means 31 and a filtering element 62. These distributed means 60 thus constitute an additional cutting arm associated with the three cutting arms of each of the phases. The distributed means 60 are controlled, in particular the duty cycle opening control, or PWM, of the conversion element 61, so as to cancel the common mode voltage of the three phases. In other words, the fourth arm allows PWM controlled control to control the common mode voltage of each converter. It is possible to control the common mode voltage of each converter, with a zero recirculation current as regulation setpoint. FIG. 8 describes the principle of active filtering of the common-mode voltage in the case of a three-phase electrical conversion. This example is not limiting, it is more widely considered distributed means 60 comprising an additional conversion element integrated electrical conversion means into N1 phases. FIG. 9 represents the parallel association of N converters 10 by means of a power supply device according to the invention. The most common case of converters fed by a continuous network and delivering three-phase AC voltages does not constitute a limit to the present invention. As shown in FIG. 9, the power supply device can comprise N converters powered by an N2 phase electrical energy network 15, which converts and feeds N1 phases. Various types of conversion means 31 may be implemented (AC / AC, DC / AC, AC / DC, DC / DC). Figure 10 shows the functional architecture of a controller implemented in the power device. It has been specified that the feed device according to the invention comprises a control member 17 capable of allocating one or more converters in real time to a load. We will describe a preferred embodiment of this controller responsible for the allocation of converters and their control. The control device envisaged by the present invention provides control of the entire power supply device by various functions. It manages in particular the parallel association of the converters, the control of load control algorithms, the entral- lation between the converters, and the control of the control algorithm specific to the converters independently of the loads. The controller can be split into several modules according to functional and time criteria. Among the functional criteria, the architecture of the selected control organ takes into account in particular the type of conversion carried out, the internal structure of the converter, the load control algorithm, or possible reconfigurations of the control device. 'food. Among the time criteria, the time constants of the protection functions, the electromechanical time constants, the control algorithm bandwidths, and the sampling and switching frequencies are taken into account.
    [0008] As shown in FIG. 10, it is envisaged a control member 17 comprising, in addition to a power stage 100, three driving modules: a low level control module 101, an intermediate control module 102 and a control module. System control 103. The principle and embodiments of these control modules are described in the following figures. FIG. 11 shows an embodiment of a low-level control module of the control member. This module 101 is in charge of fast spots dedicated to the conversion of electrical energy, as well as associated protection spots. A low level control module is associated with each converter of the device. It is preferably implemented in an electronic device integrated in the converter. for example with the power stage. Alternatively, the low level control modules of the converters can be assembled in a central electronic device. The low level control module 101 associated with a converter is independent of the electric charge. Close-up control is designed to handle fast, power-conversion-oriented tasks and associated protection. This command is independent of the load and its dedicated control algorithms. Close control is an integral part of the conversion elements making these elements intelligent and able to interface with a higher level application layer. Close Control also handles inter and intra module interactions due to interleaving and paralleling of these modules. The close control includes the low frequency recirculation current control elements with an integrated zero sequence current controller acting on the PWM control to keep the low frequency recirculation current at zero.
    [0009] The low level control module 101 comprises for each of the converters means for regulating currents. Id, Id and 10. The current control i0 ensures the servocontrol of the recirculation current to zero by acting on the PWM control of the converter. The control of currents Id and lq ensures the servocontrol of the output currents of each of the converters on setpoint values transmitted by the intermediate control module in a master / slave relationship. This particular configuration allows a balancing of the currents between the associated converters in parallel.
    [0010] In the case where the converters comprise means for limiting low frequency recirculation currents, by means of a zero sequence regulator 51 described in FIG. 7, the low level control module 101 provides the PWM control of the regulator. In the case where the converters comprise active filtering means of the common mode voltage 60, by means of an additional conversion arm 61 described in FIG. 8, the low level control module 101 controls the conversion arm. additional. The low level control is specific to each of the converters, and is independent of the parameters of the intermediate control and the system control. As shown in FIG. 11, the close-up control is in charge of control tasks dedicated to the conversion, for example: PWM modulation and generation gate control, or gate drivers in English, current mode control, or "Current mode control" in English, - Current overcurrent, or "Over-current" in English, and overheating, or "over-temperature protection" in English, - Control of low-frequency recirculation currents 30 - Control currents of high frequency recirculation for active solution The incorporation of this command in the conversion elements makes them generic and decouples the tasks related to the conversion of the tasks related to the application or system control. This emphasizes the possibility of creating a modular system and an open platform based on application-independent generic conversion modules. FIGS. 12a and 12b show an embodiment of an intermediate control module of the control member. This module 102 is in charge of the tasks dedicated to the control of the electric charges 14, the interleaving and the setting tasks. Parallel converters. The intermediate control module 102 controls the low level control modules 101 of the converters in a master / slave relationship. This relation is for example illustrated by FIG. 12a, which represents an intermediate control module providing control of the low level control modules 101 of two converters connected in parallel for supplying an electric load 14. The intermediate control 102 transmits to the converters steering command value values adapted to the allocation between the converters and the loads. For example, it sends instructions on the type of conversion to be performed, the switching frequency, the type of PWM or instructions on interlocking and paralleling in real time. The intermediate control module is independent of the energy conversion tasks supported by the low level control modules. He simply orders it. By way of example, control algorithms without a compressor, hydraulic pump or starter sensor, or bus (eg 400Hz CF, or 28Vdc) or battery charging algorithms will be implemented in the intermediate piloting module. The application brain is completely independent and decoupled from the conversion and energy conditioning tasks assumed by the close-up controls. As shown in FIG. 12b, the intermediate control module 30 is configured to provide simultaneous control of several electrical charges. For each of the electrical loads, an intermediate level control ensures the control of the low level control modules of each of the converters connected in parallel for the supply of the load. It is also contemplated by the present invention to implement a plurality of intermediate control modules to ensure redundancy of the associated control. The intermediate control module can be implemented in an independent electronic module with redundancy. FIG. 13 shows an embodiment of a control system module of the control member. This module 103 is in charge of supervision and monitoring tasks. The system control module 103 provides real-time allocation of converters to the electrical loads. It then coordinates the control of the intermediate control modules 102 and defines their setpoint parameters. The system control module 103 interfaces with the aircraft, and reconfigures the power supply device according to the information transmitted by the aircraft. It also manages the protection devices and the failures of the intermediate control modules 102. It is envisaged to implement several system control modules to ensure redundancy of the associated control. The system control module can be implemented in an independent electronic module with redundancy. It can also be implemented in an existing redundant control element, such as the BPCU or any other redundant control element present in the aircraft. This particular functional architecture of the controller is advantageous because it allows a modular electrical architecture and an open development platform. Low-level tasks are hidden and decoupled from higher-level tasks. The system is fully modular and reconfigurable from converters independent of electrical loads and the electrical power supply network. This configuration makes it possible to optimize the electrical power installed in the aircraft by real-time allocation of the sharing of the conversion resources between the N loads. This configuration also makes it possible to optimize the filtering included in the converters by interleaving them at the system level, on the source side and on the load side.
    [0011] This modular architecture is an open development platform, allowing the integration of elements of different industrial partners without particular difficulty interfacing with the rest of the device.
    [0012] The proposed architecture is a generic solution and a modular platform for integrating multiple functions sharing the same conversion resources. This architecture combines multiple functions in a power conversion center to reduce weight and costs by eliminating the need for converters dedicated to different applications. Figure 13 illustrates a cabinet integrating four applications (A, B, C, D) within the application brain. The proposed architecture is based on an open architecture allowing integration of third party applications without difficulties of intellectual properties or interfaces. It allows the integration of functions developed by different suppliers within the same firm. The distributed and partitioned control architecture, combined with high computing integrity, allows secure operation of various functions in the system with an open architecture. Each partner 20 receives a standard power brick, a development tool set and a set of development rules for the development of their control algorithms and their software code or "software code" in English. When the partner completes the development of the control algorithm and the software, the software is downloaded, or "uploaded" in English, into the application brain of the office without any problem of compatibility or intellectual property.
    权利要求:
    Claims (12)
    [0001]
    REVENDICATIONS1. Device for supplying a plurality of loads (14) from an electrical energy supply network (25), comprising a plurality of converters (16), supplied with electrical energy by the network (25), ensuring the conversion and supplying electrical energy to at least one load (14), characterized in that it comprises a control member (17) configured to associate several converters (16) in parallel to supply at least one load (14) in response to a power requirement of the at least one load (14), and in that each of the converters (16) includes distributed means (33, 43, 50, 60) for limiting recirculation currents generated by the parallel association of several converters (16).
    [0002]
    2. The device according to claim 1, wherein the distributed means (33, 43, 50) of each of the converters (16) are configured to generate a high zero sequence impedance opposing the creation of recirculation current between the converters. (16) associated in parallel.
    [0003]
    3. Device according to claim 2, each of the converters 20 (16) delivers electrical energy to the at least one load N1 phases, and whose distributed means (33a) of each of the converters (16) comprise a Zero sequence transformer (34a) coupling the N1 phases, configured to generate a high zero sequence impedance to oppose, for each phase, the creation of high frequency recirculation current between the converters (16).
    [0004]
    4. Device according to claim 2, wherein each of the converters (16) deliver electrical energy to the at least one load eh N1 phases, and whose distributed means (33b) of each of the converters (16) include for each of the N1 phases has a differential mode inductor (34b), configured to generate a high zero sequence impedance to oppose, for each phase, the creation of high frequency recirculation current between the converters (16).
    [0005]
    5. Device according to claim 3, each of the converters (16) comprises filtering means (32) associated with the transformer (34) of each of the N1 phases.
    [0006]
    6. Device according to claim 3 or 4, each of the converters (16) delivers three-phase AC electrical energy to the at least one load (14).
    [0007]
    7. Device according to one of claims 2 to 6, wherein each of the converters (16) is supplied with electrical energy by the supply network (25) in N2 phases, and whose distributed means (43) of each of the converters ( 16) comprises a transformer (44) coupling the N2 phases, configured to generate a zero sequence impedance to oppose, for each phase, the creation of high frequency recirculation current between the converters.
    [0008]
    8. Device according to claim 7, each of the converters (16) comprises filtering means (30) associated with the transformer (44) coupling the N2 phases.
    [0009]
    9. Device according to claim 7 or 8, each of the converters (16) is supplied with electrical energy by a continuous electrical network (25).
    [0010]
    10. Device according to one of claims 3 to 6, wherein the distributed means (50) of each of the converters (16) comprise a zero sequence regulator (50) configured to slave the common mode voltage of each of the converters (16). ) so as to cancel the common mode current of the N1 phases, to oppose the creation of low frequency recirculation current between the converters (16).
    [0011]
    Apparatus according to claim 1, wherein the distributed means (60) of each of the converters (16) are configured to cancel common mode voltages differences between the converters (16) associated in parallel.
    [0012]
    12. Device according to claim 11, whose converters deliver energy to the at least one charge in N1 phases, and whose distributed means (60) of each of the converters (16) comprise a conversion element (61). complementary to the conversion means (31) in N1 phases and a filter element (62), allowing active mode common voltage filtering in each of the converters (16).
    类似技术:
    公开号 | 公开日 | 专利标题
    EP2887519A2|2015-06-24|Modular, reconfigurable device for converting electric power
    CA2667270C|2015-06-23|System for generating, converting, distributing and electrically starting on board an aircraft
    CN105518972B|2019-03-29|The power system for aircraft with dual hybrid energy sources
    EP2732530B1|2018-01-10|Rapid multi-level recharge system
    FR2946810A1|2010-12-17|REVERSIBLE FAST CHARGE DEVICE FOR ELECTRIC VEHICLE
    FR2943188A1|2010-09-17|FAST CHARGING DEVICE FOR AN ELECTRIC VEHICLE.
    FR2907760A1|2008-05-02|Power supply system for aircraft, has electric cores having input stage with alternate current/direct current converter, switching matrix that connect power modules through inductor, and switching assembly connected to charge
    EP2260559A2|2010-12-15|Electrical network
    EP2697886A1|2014-02-19|Device for charging a battery of a motor vehicle on the basis of a single-phase power supply network, and method of controlling the device
    EP3403872A1|2018-11-21|Electric charging system for hybrid or electric vehicle
    WO2007080196A1|2007-07-19|20° phase-shifting autotransformer
    EP2783443A1|2014-10-01|Secured and regulated continuous power supply system with multiple inputs
    WO2014049254A1|2014-04-03|System for charging a motor vehicle battery
    EP3175527B1|2018-06-06|High-voltage direct current power supply system for an aircraft
    EP2859641B1|2021-01-27|Charging device with adaptative input and charging method
    EP3605818A1|2020-02-05|Dc-dc resonant voltage converter
    EP3208909B1|2019-08-14|Mixed ac-dc electrical power distribution system for supplying variable-frequency loads and fixed-frequency loads
    EP3505402A1|2019-07-03|Electrical harness
    WO2013188009A1|2013-12-19|Multi-port reconfigurable battery
    EP3227137B1|2020-04-08|Improved direct-current converter and power supply device
    EP2992585B1|2017-05-31|System and method for charging the battery of an electric or hybrid vehicle
    FR3064126A1|2018-09-21|ELECTRICAL SYSTEM FOR MOTOR VEHICLE WITH ELECTRIC OR HYBRID MOTOR
    FR3026581A1|2016-04-01|CONTINUOUS ENERGY TRANSFER
    FR3010593A1|2015-03-13|SYSTEM FOR CONTROLLING AN ELECTRICAL CHARGE
    FR3068532A1|2019-01-04|ELECTRICAL POWER DISTRIBUTION BOX FOR AN AIRCRAFT DRIVING NETWORK AND CORRESPONDING POWER SUPPLY SYSTEM
    同族专利:
    公开号 | 公开日
    CA2875088A1|2015-06-18|
    EP2887519A2|2015-06-24|
    BR102014031848A2|2017-11-21|
    FR3015145B1|2017-07-07|
    EP2887519A3|2015-08-05|
    US20160329705A1|2016-11-10|
    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    US20040017689A1|2002-07-25|2004-01-29|General Electric Company|Cross current control for power converter systems and integrated magnetic choke assembly|
    FR2899734A1|2006-04-05|2007-10-12|Thales Sa|DEVICE FOR SUPPLYING A PLURALITY OF LOADS FROM AN ELECTRIC POWER SUPPLY NETWORK|
    US7564703B1|2007-04-17|2009-07-21|Rockwell Automation Technologies, Inc.|Method and apparatus for synchronized parallel operation of PWM inverters with limited circulating current|
    WO2011160644A2|2010-06-24|2011-12-29|Vestas Wind Systems A/S|Method of pwm switching for parallel converters|
    US20120106210A1|2010-10-27|2012-05-03|Rockwell Automation Technologies, Inc.|Multi-phase power converters and integrated choke therfor|
    FR603002A|1924-10-18|1926-04-07|Friend Bentley Elements Compan|Improvements to internal combustion machines|
    US7233506B1|2006-04-03|2007-06-19|Derek Albert Paice|Low kVA/kW transformers for AC to DC multipulse converters|EP3254372A1|2015-02-05|2017-12-13|Otis Elevator Company|Drive and control for six-phase electrical machines with negligible common-mode voltage|
    CA2982351C|2015-04-10|2021-08-10|Epc Power Corporation|Reconfigurable power converter|
    US9985566B2|2015-05-29|2018-05-29|Otis Elevator Company|Dual three-phase electrical machine and drive with negligible common-mode noise|
    EP3255774A1|2016-06-07|2017-12-13|GE Energy Power Conversion Technology Ltd|System for converting electric energy supplied by a network and conversion method implemented by means of such a conversion system|
    ES2646670B1|2016-06-09|2018-10-10|Bsh Electrodomésticos España, S.A.|Home appliance device and procedure with a home appliance device|
    EP3301805A1|2016-09-30|2018-04-04|Fronius International GmbH|Method for operating an inverter and inverter|
    US20190319549A1|2016-11-16|2019-10-17|Schneider Electric Solar Inverters Usa, Inc.|Interleaved parallel inverters with integrated filter inductor and interphase transformer|
    FR3078845A1|2018-03-08|2019-09-13|Thales|ELECTRICAL ARCHITECTURE OF CONVERTER CONTROL AND AIRCRAFT COMPRISING ARCHITECTURE|
    US11088690B2|2018-10-12|2021-08-10|Autonics Corporation|Switch|
    DE102019106472A1|2019-03-14|2020-09-17|Sma Solar Technology Ag|Inverter with several DC / AC converters and a common sine filter and power generation system with such an inverter|
    FR3095725A1|2019-05-02|2020-11-06|Thales|Inductive filtering device and electrical architecture implementing the filtering device|
    EP3913785A4|2020-05-20|2021-11-24|Goodrich Control Sys|Distributed current balancing control|
    CN112701952B|2020-12-28|2021-12-24|广东工业大学|PWM method and system for minimum effective value of current ripple of three-phase two-level inverter|
    法律状态:
    2015-11-23| PLFP| Fee payment|Year of fee payment: 3 |
    2016-11-28| PLFP| Fee payment|Year of fee payment: 4 |
    2017-11-27| PLFP| Fee payment|Year of fee payment: 5 |
    2019-11-28| PLFP| Fee payment|Year of fee payment: 7 |
    2020-11-25| PLFP| Fee payment|Year of fee payment: 8 |
    2021-11-26| PLFP| Fee payment|Year of fee payment: 9 |
    优先权:
    申请号 | 申请日 | 专利标题
    FR1302974A|FR3015145B1|2013-12-18|2013-12-18|MODULAR AND RECONFIGURABLE ELECTRIC POWER CONVERTING DEVICE|FR1302974A| FR3015145B1|2013-12-18|2013-12-18|MODULAR AND RECONFIGURABLE ELECTRIC POWER CONVERTING DEVICE|
    CA2875088A| CA2875088A1|2013-12-18|2014-12-17|Modular, reconfigurable conversion device for electrical power|
    US14/574,852| US20160329705A1|2013-12-18|2014-12-18|Modular and reconfigurable electrical power conversion device|
    EP14198743.8A| EP2887519A3|2013-12-18|2014-12-18|Modular, reconfigurable device for converting electric power|
    BR102014031848-8A| BR102014031848B1|2013-12-18|2014-12-18|DEVICE FOR SUPPLYING DIFFERENT LOADS FROM AN ELECTRIC POWER SUPPLY NETWORK|
    [返回顶部]